energies
Article Design of a Novel Modular Axial-Flux Double Rotor Switched Reluctance Drive
Pere Andrada * , Balduí Blanqué , Eusebi Martínez, José Ignacio Perat, José Antonio Sánchez and Marcel Torrent
GAECE, Department of Electrical Engineering (DEE), Universitat Politècnica de Catalunya UPC BARCELONATECH. EPSEVG, Víctor Balaguer 1, 08800 Vilanova i la Geltrú, Spain; [email protected] (B.B.); [email protected] (E.M.); [email protected] (J.I.P.); [email protected] (J.A.S.); [email protected] (M.T.) * Correspondence: [email protected]
Received: 11 February 2020; Accepted: 28 February 2020; Published: 4 March 2020
Abstract: Nowadays, there is a renewed interest in switched reluctance machines and especially in axial-flux switched reluctance machines (AFSRM). This paper presents a comprehensive design procedure for modular AFSRM with an inner stator and two exterior rotors that have a new distribution of the stator and rotor poles, resulting in short magnetic paths with no flux reversal. After a description of the proposed machine, the output torque equation is derived from a simplified non-linear energy conversion loop and guidelines for its design are given. Once the preliminary sizing has been carried out the different modules of the AFSRM, the magnetically active parts made with SMC, are reshaped or refined using 3D printing and 3D electromagnetic finite element analysis until they reach their definitive shape and dimensions. Finally, an AFSRM has been built following the proposed design procedure and has been validated by experimental measurements.
Keywords: switched reluctance machines; axial-flux machines; modular construction; soft magnetic composites; design of electric drives
1. Introduction Nowadays, many applications such as fans, pumps, machine tools, and electric vehicles demand the use of axial-flux electric machines. Most usual axial-flux electric machines are DC commutator motors, brushless DC motors, or synchronous motors, all of them excited with permanent magnets. These machines can be designed in many diverse ways, such as single stage or multistage, with or without armature slots, with or without armature core, or with internal or external rotors to better adapt to the requirements of application in which they have to be used [1]. The development of these machines has gone in parallel with that of the permanent magnets. However, the abrupt increase of the raw material cost in rare earth permanent magnets happened in 2011, shifted research in the field of electrical machines towards topologies with a lower volume of permanent magnets and even without permanent magnets. This circumstance has renewed the interest for switched reluctance machines, especially in the field of electric traction [2]. Some studies carried out in axial-flux switched reluctance motors (AFSRM) demonstrate that they have higher torque density than conventional radial flux switched reluctance machines [3]. The design of AFSRM is not something new; in 1990 Krishnan et al. [4] were the first to give the basics of the design of AFSRM. Later, Arihara and Akatsu proposed the basic design methodology of a single side AFSRM [5], Labak and Kar [6] presented the design procedure and a prototype of a novel five-phase pancake-shaped AFSRM. Madhavan and Fernandes [7,8] developed a new segmented AFSRM with higher number of rotor segments and gave the basis of its design. Ebrahimi and Feyzi made some contributions to the design of AFSRM
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Energiesmodular2020, stator13, 1161 [9]. Recently, Lin proposed a variation of the output equation for this type of machine2 of 17 [10] and Torkaman et al. [11] provided a review of the design of AFSRM including a comparison, considering the assessment of some performance indices among different topologies. This paper withproposes modular a new stator procedure, [9]. Recently, taking Lin into proposed account saturation, a variation for of the the sizing output of equation a particular for thistype type of an ofAFSRM machine with [10 ]an and inner Torkaman stator and et al.two [11 exterior] provided rotors a reviewthat have of thea new design distribution of AFSRM of the including stator and a comparison,rotor poles consideringresulting in theshort assessment magnetic ofpaths some with performance no flux reversal indices that among have di beenfferent presented topologies. in [12–16]. This paperThe machine proposes has a new been procedure, built modularly taking intowith account stator and saturation, rotor poles for themade sizing with of SMC a particular parts. The type paper of anis AFSRM organized with as an follows. inner stator In Section and two 2, a exterior description rotors of that the haveproposed a new AFSRM distribution is presented. of the stator Section and 3 rotordevelops poles resultingthe output in torque short magnetic equation pathsof the with AFSRM. no flux In Section reversal 4 that guidelines have been for presentedsizing the AFSRM in [12–16 are]. Thegiven. machine Section has 5 beenexposes built a methodology modularly with of design stator andof an rotor AFSRM, poles intended made with for SMCthe propulsion parts. The of paper a light iselectric organized scooter, as follows. following In Sectionthe aforementioned2, a description sizing of the guidelines. proposed The AFSRM experimental is presented. assessment Section of3 the developsdesigned the AFSRM output is torque presented equation in Section of the AFSRM. 6. Finally, In Section in Section4 guidelines 7, conclusions for sizing from the this AFSRM study are are given.drawn. Section 5 exposes a methodology of design of an AFSRM, intended for the propulsion of a light electric scooter, following the aforementioned sizing guidelines. The experimental assessment of the designed2. Description AFSRM of is the presented Proposed in Section Axial‐6Flux. Finally, Switched in Section Reluctance7, conclusions Machines from (AFSRM) this study Machine are drawn.
2. DescriptionIn this paper, of the a Proposed three phase Axial-Flux AFSRM Switchedwith an inner Reluctance stator of Machines twelve poles (AFSRM) and two Machine outer rotors with ten poles is designed. It is a particular case of a new type of AFSRM with a new arrangement of In this paper, a three phase AFSRM with an inner stator of twelve poles and two outer rotors with the stator and the rotor poles and with short flux paths without flux reversal, which has been ten poles is designed. It is a particular case of a new type of AFSRM with a new arrangement of the previously reported [13]. The ten ferromagnetic poles of each rotor are joined on the opposite side of stator and the rotor poles and with short flux paths without flux reversal, which has been previously the air‐gap, by means of an annular disk also of ferromagnetic material. The stator is formed by reported [13]. The ten ferromagnetic poles of each rotor are joined on the opposite side of the air-gap, twelve poles of triangular shape of ferromagnetic material, sticking out with the same length at both by means of an annular disk also of ferromagnetic material. The stator is formed by twelve poles ends of an aluminum structural disk attached to a hollow shaft. An exploded view of such a motor is of triangular shape of ferromagnetic material, sticking out with the same length at both ends of an shown in Figure 1. aluminum structural disk attached to a hollow shaft. An exploded view of such a motor is shown in Figure1.
(a) (b)
FigureFigure 1. 1.(a ()a Exploded) Exploded view view of of the the proposed proposed axial-flux axial‐flux switched switched reluctance reluctance machines machines (AFSRM) (AFSRM) (left (left),), (b()b representation) representation of of the the flux flux path path when when there there is is alignment alignment between between stator stator and and rotor rotor poles poles (right (right)[)15 [15].].
AsAs it it is is depicted depicted in in Figure Figure2, two2, two coils coils are are wound wound in in both both opposite opposite ends ends of of the the stator stator poles poles and and connectedconnected in in series. series. The The coils coils of two of two adjacent adjacent stator stator poles poles are also are connected also connected in series in forming series aforming double a electromagnet.double electromagnet. Having the Having described the machinedescribed six machine double six electromagnets, double electromagnets, each phase iseach formed phase by is connectingformed by in connecting parallel the in two parallel double the electromagnets two double diametrically electromagnets opposed. diametrically The terminals opposed. of theThe phaseterminals windings of the leave phase the windings machine leave through the themachine hollow through shaft. the hollow shaft.
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(a) (b)
Figure 2. (a) schematic drawing of the coil’s arrangement of the two double electromagnets diametrically opposed (stator poles 1–2 and 7–8) [15], connected in parallel to form phase A. (b) upper view of the layout of the different phases (red: Phase A; blue: Phase B and black: Phase C).
3. Output Torque Equation for AFSRM The starting point of the( adesign) of electric rotating machines is the output( torqueb) equation, which relates the torque with the main dimensions (bore diameter and axial length in radial flux machines), FigureFigure 2. (2.a ) schematic(a) schematic drawing drawing of the coil’sof the arrangement coil’s arrangement of the two doubleof the electromagnetstwo double electromagnets diametrically magneticopposeddiametrically loading, (stator andopposed poles electric 1–2 (stator and loading 7–8) poles [15 1–2[17].], connected and In 7–8) this [15], paper, in parallel connected the to output form in parallel phase torque to A. form equation (b) upper phase view ofA. the(b) of upperAFSRM the is derivedlayoutview not of the of dilayoutthefferent expression of phases the different (red: of the Phase phases average A; (red: blue: torque Phase Phase A;disregarding B blue: and black:Phase PhaseB the and saturation C).black: Phase [4,7,9] C). but of the energy converted into mechanical work in each stroke, energy conversion loop, represented by the 3. Output Torque Equation for AFSRM area3. Output W (OACEO) Torque shown Equation in Figure for AFSRM 3 [18], multiplied by the number of strokes per revolution, s, given by: The starting point of the design of electric rotating machines is the output torque equation, which The starting point of the design of electricm N rotating machines is the output torque equation, which relates the torque with the main dimensions (bore diameter and axial length in radial flux machines), relates the torque with the main dimensionss (bore diameter and axial length in radial flux machines),(1) magnetic loading, and electric loading [17]. In this2π paper, the output torque equation of the AFSRM is magnetic loading, and electric loading [17]. In this paper, the output torque equation of the AFSRM wherederived m not is the of thenumber expression of phases of the and average NR the torque number disregarding of rotor poles. the saturation [4,7,9] but of the energy is derived not of the expression of the average torque disregarding the saturation [4,7,9] but of the convertedIf the phase into mechanical resistance is work neglected in each and stroke, the aligned energy magnetization conversion loop, curve represented is approximated by the by area two W energy converted into mechanical work in each stroke, energy conversion loop, represented by the straight(OACEO) lines, shown OD in with Figure a slope3[18], Lau, multiplied and DB by parallel the number to the of unaligned strokes per magnetization revolution, s, givencurve by: also a area W (OACEO) shown in Figure 3 [18], multiplied by the number of strokes per revolution, s, given straight line, OA, with a slope Lu [15]. The current between points A and C is flat‐topped and has a by: m NR value of IB, being C the point where solid states switches=m N turn‐off in which flux linkage, ψs, is equal (1)to 2π kd Las IB, being Las the saturated inductance, s slope of the straight line OB, and kd the magnetic flux 2π (1) linkagewhere m ratio. is the number of phases and NR the number of rotor poles. where m is the number of phases and NR the number of rotor poles. If the phase resistance is neglected and the aligned magnetization curve is approximated by two straight lines, OD with a slope Lau, and DB parallel to the unaligned magnetization curve also a straight line, OA, with a slope Lu [15]. The current between points A and C is flat‐topped and has a value of IB, being C the point where solid state switches turn‐off in which flux linkage, ψs, is equal to kd Las IB, being Las the saturated inductance, slope of the straight line OB, and kd the magnetic flux linkage ratio.
FigureFigure 3. 3. EnergyEnergy conversion conversion loop. loop.
If the phase resistance is neglected and the aligned magnetization curve is approximated by two straight lines, OD with a slope Lau, and DB parallel to the unaligned magnetization curve also a straight line, OA, with a slope Lu [15]. The current between points A and C is flat-topped and has a value of IB, being C the point where solid state switches turn-off in which flux linkage, ψs, is equal to
Figure 3. Energy conversion loop.
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kd Las IB, being Las the saturated inductance, slope of the straight line OB, and kd the magnetic flux linkage ratio. With these assumptions from Figure3, the torque [19] can be evaluated as:
mN T = sW = R k k L I2 (2) 2π d L as B
Being, kL, inductance ratio given by: Lu 1 Las Lu kL = 1 1 kd − (3) −Lau −2 Lau Lu − The flux linkage is the product of the number of turns of the phase, Nf, by the magnetic flux density in the stator pole (magnetic loading), Bp, and by the area of the stator pole. Due to the particular geometry of the AFSRM, with Do and Di which are outer and inner stator diameters, respectively, and considering that the stator pole angle in the average stator diameter is approximately equal to a stroke, the flux linkage is given by: π ψ 2 2 S= Las IB= Bp Do Di Nf (4) 2NRm − Considering the linear current density (electric loading) as:
2m N I 2m N I 4m N I A = f B = f B = f B (5) ( + ) Do Di πDAV π(D0 + Di) π 2
The torque, substituting (3)–(5) in (2) is:
π 2 2 T = k k BpA D D (Do + D ) (6) 16m d L o − i i Introducing the relationship between inner and outer diameter, diameter ratio ξ, as:
D ξ = i (7) Do
Then the torque equation can be expressed as:
π 3 2 T = k k BpAD (1 + ξ) (1 ξ) (8) 16m d L o − An alternative expression is: 2 T = To(1 + ξ) (1 ξ) (9) − With: π T = k k B AD3 (10) o 16m d L p o Therefore, the torque per unit is given by:
T t = = (1 + ξ)2(1 ξ) (11) To −
The torque per unit with respect to the diameter ratio is depicted in Figure4, where it can be seen that the maximum torque per unit is achieved when the diameter ratio is one third, nevertheless good values of ξ can be obtained in the margin between one fifth and one half. Energies 2020, 13, 1161 5 of 17 Energies 2020, 13, x FOR PEER REVIEW 5 of 17
Figure 4.4. Torque p.u.,p.u., t,t, versusversus diameterdiameter ratioratio ξξ..
InIn regardsregards toto thethe otherother termsterms ofof the the Formula formula (10)(10) thethe followingfollowing considerationsconsiderations shouldshould bebe takentaken intointo account:account:
• BBpp, magnetic loading, maximum stator pole magnetic flux flux density, itit shouldshould bebe lowerlower thanthan • magneticmagnetic fluxflux densitydensity ofof saturationsaturation ofof thethe magneticmagnetic material material used used • A,A, electricelectric loadingloading oror linearlinear currentcurrent density,density, dependsdepends onon coolingcooling conditionsconditions ofof thethe machine,machine, itit • shouldshould bebe comprisedcomprised betweenbetween 75,00075,000 andand 200,000200,000 A A/m./m. • kkd, fluxflux linkage duty cycle, usually isis betweenbetween 0.50.5 andand 0.8.0.8. • d • kkL, inductance ratio, depends on thethe levellevel of saturationsaturation ofof thethe machinemachine • L 4.4. Design Guidelines for the Sizing of the Proposed AFSRMAFSRM TheThe AFSRMAFSRM designdesign procedureprocedure startsstarts withwith thethe completecomplete definitiondefinition ofof allall thethe specificationsspecifications andand restrictionsrestrictions thatthat thethe applicationapplication imposesimposes onon thethe machinemachine toto bebe designed.designed. After thethe selectionselection ofof thethe materialsmaterials toto bebe used,used, thethe mainmain dimensionsdimensions areare obtainedobtained usingusing thethe outputoutput torquetorque equation.equation. Then, by meansmeans ofof simplesimple formulas,formulas, thethe geometrical dimensionsdimensions ofof thethe stator, thethe numbernumber ofof turnsturns ofof thethe phase windings,windings, andand thethe geometricalgeometrical dimensionsdimensions ofof thethe twotwo rotorsrotors are are determined. determined.
4.1.4.1. Design of Stator Polar Pieces and Determination ofof thethe NumberNumber ofof TurnsTurns PerPer Pole Pole TheThe statorstator polepole piecespieces areare arrangedarranged accordingaccording to FigureFigure5 5,, where where γ γ thethe angleangle betweenbetween axesaxes ofof consecutiveconsecutive doubledouble electromagnets,electromagnets, withwith ZZ numbernumber ofof doubledouble electromagnets,electromagnets, is is given given by: by: 360o γ 360 (12) γ = Z (12) Z And δ is the angle between axes of stator poles of two consecutive double electromagnets: And δ is the angle between axes of stator poles of two consecutive double electromagnets: 360 N Z δ o (13) 360 [ZN NR Z] δ = − (13) ZNR
The polar pieces of the stator have a triangular shape and considering that in the stator pieces whose symmetry axis form an angle δ the inner sides of these pieces are parallel, that is, the distance ws is constant between Do and Di along the two stator poles, the angle ϕs is approximately:
ϕs = 2δ(1 ξ) (14) −
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Figure 5. Stator section showing the disposition and dimensions of stator poles.
InThe practice, polar pieces it could of bethe advisable, stator have in a order triangular to reduce shape stator and mass, considering that: that in the stator pieces whose symmetry axis form an angle δ the inner sides of these pieces are parallel, that is, the distance ws is constant between Do and Di along the ϕtwos < stator2δ(1 poles,ξ) the angle φs is approximately: (15) − Being: φ 2δ 1 ξ (14) δ In practice, it could be advisable, in orderws =to Dreducesin stator mass, that: (16) i 2
Therefore, the area of a stator pole, Asp,φ is: 2𝛿 1 ξ (15)
Being: 1 2 ϕs Asp= (D0 Di) tg (17) 4 − δ 2 w D sin (16) Otherwise, the voltage equation of the AFSRM can2 be approximated, being ω the speed of the machineTherefore, and neglecting the area of phase a stator resistance, pole, A by:sp, is: 1 φ dψ ∆ψ ∆ψ θ ∆ψ s Asp= D s D tgs ∆ s (17) U = RfI 4 2 = ω (18) dt − ≈ ∆t ≈ ∆θ ∆t ∆θ Otherwise, the voltage equation of the AFSRM can be approximated, being ω the speed of the From Figure3, the increment of flux linkage between points A and C can be given by: machine and neglecting phase resistance, by:
d∆ψψ = k LasΔψI = kΔψN ΔθBpAspΔψ (19) U Rs I d B d f ω (18) dt Δt Δθ Δt Δθ And the variation of position between points A and C can be approximate by: From Figure 3, the increment of flux linkage between points A and C can be given by: Δψ = k L I = 2kπ N B A ∆ θas sp (20)(19) ≈ mNR And the variation of position between points A and C can be approximate by: Then the number of turns per phase, Nf, is given by: 2π Δθ (20) 2mNπU Nf= (21) m NRkdBpAspω Then the number of turns per phase, Nf, is given by:
The number of turns per coil, Np, depends on the2π numberU of double electromagnets per phase, two N = (21) in the AFRM considered, each consisting of fourm N coils, k B and Asp ofω their connection (x = 1 series connection and x = 1/2 for parallel connection), thus: The number of turns per coil, Np, depends on the number of double electromagnets per phase, two in the AFRM considered, each consisting of four coils, and of their connection (x = 1 series connection and x = 1/2 for parallel connection), thus:
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N N =N (22) N =p 8xf (22) p 8x The wire section, sc, considering the connection of the double electromagnets per phase, is determinedThe wire by section, the ratio sc ,between considering RMS the (Root connection Mean Square of the value) double phase electromagnets current I and per the phase, current is determineddensity, Δ, as: by the ratio between RMS (Root Mean Square value) phase current I and the current density, ∆, as: xx I I s s= = (23)(23) c ∆Δ
TheThe copper copper area, area, A Acucu,, intointo aa slotslot isis approximatelyapproximately equalequal to: to:
Acu 2N s = k h w (24) Acu = 2Npsc= kvhews (24)
Being kv the slot fill factor, and he the height of the protruding stator pole at one side of the structuralBeing disk: kv the slot fill factor, and he the height of the protruding stator pole at one side of the structural disk: 2N2Np ssc he h= = (25)(25) kkvw ws
TheThe total total height height of of a a stator stator pole, pole, h hetet,, is:is: h 2h h het et= 2he + hcece (26)(26)
With hce thickness of stator structural disk, Figure 6. With hce thickness of stator structural disk, Figure6.
Figure 6. Arrangement of stator poles into the structural disk. Figure 6. Arrangement of stator poles into the structural disk.
4.2.4.2. Design Design of of Rotor Rotor Pole Pole and and Yoke Yoke TheThe rotor rotor pole pole pieces pieces are are equally equally displaced, displaced, Figure Figure7 ,7, by by the the angle angleα α equalequal to: to: 360 α 360o (27) α = N (27) NR The rotor poles have the same length, half the difference between outer an inner diameter than The rotor poles have the same length, half the difference between outer an inner diameter than stator poles. The angle φr should verify: stator poles. The angle ϕr should verify: φ φ ϕr > ϕs (28)(28) TheThe height height of of the the rotor rotor pole, pole, Figure Figure8 ,8, can can be be estimated estimated approximately approximately by: by: 1 h 1 h (29) hr 3he (29) ≈ 3
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Figure 7. Rotor section showing disposition and dimensions of rotor poles.
The thickness of the rotor yoke, hcr, is determined considering that the yoke area is approximately half than the rotor pole area in order to reduce mass and despite this increase the flux density in the rotor yoke, therefore the yoke area can be expressed by: