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onsemi and and other names, marks, and brands are registered and/or common law trademarks of Semiconductor Components Industries, LLC dba “onsemi” or its affiliates and/or subsidiaries in the United States and/or other countries. onsemi owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. A listing of onsemi product/patent coverage may be accessed at www.onsemi.com/site/pdf/Patent-Marking.pdf. onsemi reserves the right to make changes at any time to any products or information herein, without notice. The information herein is provided “as-is” and onsemi makes no warranty, representation or guarantee regarding the accuracy of the information, product features, availability, functionality, or suitability of its products for any particular purpose, nor does onsemi assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. Buyer is responsible for its products and applications using onsemi products, including compliance with all laws, regulations and safety requirements or standards, regardless of any support or applications information provided by onsemi. “Typical” parameters which may be provided in onsemi data sheets and/ or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. onsemi does not convey any license under any of its intellectual property rights nor the rights of others. onsemi products are not designed, intended, or authorized for use as a critical component in life support systems or any FDA Class 3 medical devices or medical devices with a same or similar classification in a foreign jurisdiction or any devices intended for implantation in the human body. Should Buyer purchase or use onsemi products for any such unintended or unauthorized application, Buyer shall indemnify and holdonsemi and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that onsemi was negligent regarding the design or manufacture of the part. onsemi is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner. Other names and brands may be claimed as the property of others. AND8177/D

Audio Circuits Using the NE5532/4

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APPLICATION NOTE Audio Circuits Using the NE5532/34 preamp, input buffer, 5--band equalizer, and mixer. The following will explain some of ON Semiconductors Although the circuitdesign is not new, its performanceusing low noise op amps and show their use in some audio the 5532 has been improved. applications. The RIAA preamp section is a standard compensation configuration with low frequency boost provided by the Description Magnetic cartridge and the RC network in the op amp The 5532 is a dual high--performance low noise loop. Cartridge loading is accomplished via R1. operational . Compared to most of the standard 47 kΩ was chosen as a typical value, and may differ from operational , such as the 1458, it shows better cartridge to cartridge. noise performance, improved output drive capability and The Equalizer section consists of an input buffer, 5 active considerably higher small--signal and power bandwidths. variable band pass/notch (depending on R9’s setting) filters, This makes the device especially suitable for application and an output summing amplifier. The input buffer is a in high quality and professional audio equipment, standard unity gain design providing impedance matching instrumentation and control circuits, and telephone channel between the preamplifier and the equalizer section. Because amplifiers. The op amp is internally--compensated for gains the 5532 is internally--compensated, no external equal to one. If very low noise is of prime importance, it is compensation is required. The 5--band active filter section is recommended that the 5532A version be used which has actually five individual active filters with the same feedback guaranteed noise voltage specifications. design for all five. The main difference in all five stages is APPLICATIONS the values of C5 and C6, whichare responsiblefor settingthe ON Semiconductors 5532 High--Performance Op Amp is center frequency of each stage. Linear pots are an ideal amplifier for use in high quality and professional recommended for R9. To simplify use of this circuit, a audio equipment which requires low noise and low component value table is provided, which lists center distortion. frequencies and their associated capacitor values. Notice The circuit (Figure 1) included in this application note has that C5 equals 10 × C6 and the value of R8 and R10 are been assembled on a PC board, and tested with actual audio related to R9 by a factor of 10 as well. The values listed in input devices (Tuner and Turntable). It consists of a the table are common and easily found standard values. Recording Industry Association of America (RIAA)

C5 Equ In 5 C1 RIAA Out + RIAA 3 7R7R8 R7 + 1/2 5532 1 R5 6 1/2 5532 -- 2 R9 C6 R9 R1 -- R5 R11

R2 R3 2 -- C7 R10 + 1 6 FLAT C2 C3 1/2 5532 -- TO VOL./ 3 7 BAL AMP + 1/2 5532 5 + EQUALIZE R4 REPEAT ABOVE CIRCUIT FOR DESIRE NO. OF C4 STAGES.

R12

Figure 1. RIAA -- Equalizer Schematic

© Semiconductor Components Industries, LLC, 2005 1 Publication Order Number: November, 2005 -- Rev. 0 AND8177/D AND8177/D

RIAA Equalization Audio Preamplifier Using sub--audible tones,they becomequite objectionablebecause NE5532A the speakers try to reproduce these tones. This causes With the onset of new recording techniques with non--linearities when the actual recorded material is sophisticated playback equipment, a new breed of low noise amplified and converted to sound waves. operational amplifiers was developed to complement the The RIAA has proposed a change in its standard playback state--of--the--art in audio reproduction. The first ultra--low response curve in order to alleviate some of the problems noise op amp introduced by ON Semiconductors was called thatwerepreviouslydiscussed.Thechangesoccurprimarily the NE5534A. This is a single with at the low frequency range with a slight modification to the high frequency range (See Figure 2). Note that the response less than 4nV∕ Hz input noise voltage. The NE5534A is internally--compensated at a gain of three. This device has peak for the bass section of the playback curve now occurs been used in many audio preamp and equalizer (active filter) at 31.5 Hz and begins to roll off below that frequency. The applications since its introduction. roll--off occurs by introducing a fourth RC network with a Many of the amplifiers that are being designed today are 7950 ms time constant to the three existing networks that DC--coupled. This means that very low frequencies make up the equalization circuit. The high end of the (2--15 Hz) are being amplified. These low frequencies are equalization curve is extended to 20 kHz, because common to turntables because of rumble and tone arm recordings at these frequencies are achievable on many resonances. Since the amplifiers can reproduce these current discs.

-- 2 5 OLD RIAA -- 2 0

-- 1 5

-- 1 0 NEW RIAA -- 5

0

(dB) 5

10 15

20 25

30

1 10 100 (Hz) 1K 10K 100K

Figure 2. Proposed RIAA Playback Equalization

-- 1 5 V

.1 mF .27 mF INPUT + 3 8 TO LOAD 47 KΩ NE5532A 1 2 4 -- .1 mF -- 1 5 V

49.9 KΩ 49.9 Ω

.056 mF 4.99 KΩ

47 mF

.015 mF

NOTE: All resistors are 1% metal film.

Figure 3. RIAA Phonograph Preamplifier Using the NE5532A

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COMPONENT VALUES FOR FIGURE 1 R8 = 25 kΩ R8 = 50 kΩ R8 = 100 kΩ R7 = 2.4 kΩ R9 = 240 kΩ R7 = 5.1 kΩ R9 = 510 kΩ R7 = 10 kΩ R9 = 1 megΩ

fO C5 C6 fO C5 C6 fO C5 C6 23 Hz 1 mF 0.1 mF 25 Hz 0.47 mF 0.047 mF 12 Hz 0.47 mF 0.047 mF 50 Hz 0.47 mF 0.047 mF 36 Hz 0.33 mF 0.033 mF 18 Hz 0.33 mF 0.033 mF 72 Hz 0.33 mF 0.033 mF 54 Hz 0.22 mF 0.022 mF 27 Hz 0.22 mF 0.022 mF 108 Hz 0.22 mF 0.022 mF 79 Hz 0.15 mF 0.015 mF 39 Hz 0.15 mF 0.015 mF 158 Hz 0.15 mF 0.015 mF 119 Hz 0.1 mF0.01mF 59 Hz 0.1 mF0.01mF 238 Hz 0.1 mF0.01mF 145 Hz 0.082 mF 0.0082 mF 72 Hz 0.082 mF 0.0082 mF 290 Hz 0.082 mF 0.0082 mF 175 Hz 0.068 mF 0.0068 mF 87 Hz 0.068 mF 0.0068 mF 350 Hz 0.068 mF 0.0068 mF 212 Hz 0.056 mF 0.0056 mF 106 Hz 0.056 mF 0.0056 mF 425 Hz 0.056 mF 0.0056 mF 253 Hz 0.047 mF 0.0047 mF 126 Hz 0.047 mF 0.0047 mF 506 Hz 0.047 mF 0.0047 mF 360 Hz 0.033 mF 0.0033 mF 180 Hz 0.033 mF 0.0033 mF 721 Hz 0.033 mF 0.0033 mF 541 Hz 0.022 mF 0.0022 mF 270 Hz 0.022 mF 0.0022 mF 1082 Hz 0.022 mF 0.0022 mF 794 Hz 0.015 mF 0.0015 mF 397 Hz 0.015 mF 0.0015 mF 1588 Hz 0.015 mF 0.0015 mF 1191 Hz 0.01 mF 0.001 mF 595 Hz 0.01 mF 0.001 mF 2382 Hz 0.01 mF 0.001 mF 1452 Hz 0.0082 mF 820 pF 726 Hz 0.0082 mF 820 pF 2904 Hz 0.0082 mF 820 pF 1751 Hz 0.0068 mF 680 pF 875 Hz 0.0068 mF 680 pF 3502 Hz 0.0068 mF 680 pF 2126 Hz 0.0056 mF 560 pF 1063 Hz 0.0056 mF 560 pF 4253 Hz 0.0056 mF 560 pF 2534 Hz 0.0047 mF 470 pF 1267 Hz 0.0047 mF 470 pF 5068 Hz 0.0047 mF 470 pF 3609 Hz 0.0033 mF 330 pF 1804 Hz 0.0033 mF 330 pF 7218 Hz 0.0033 mF 330 pF 5413 Hz 0.0022 mF 220 pF 2706 Hz 0.0022 mF 220 pF 10827 Hz 0.0022 mF 220 pF 7940 Hz 0.0015 mF 150 pF 3970 Hz 0.0015 mF 150 pF 15880 Hz 0.0015 mF 150 pF 11910 Hz 0.001 mF 100 pF 5955 Hz 0.001 mF 100 pF 23820 Hz 0.001 mF 100 pF 14524 Hz 820 pF 82 pF 7262 Hz 820 pF 82 pF 17514 Hz 680 pF 68 pF 8757 Hz 680 pF 68 pF 21267 Hz 560 pF 56 pF 10633 Hz 560 pF 56 pF 12670 Hz 470 pF 47 pF 18045 Hz 330 pF 33 pF

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NE5534 Description R1 C1 circuit deleted, the device slew rate falls to The 5534 is a single high--performance low noise approximately 7 V/ ms. The input waveform will reach 2 operational amplifier. Compared to other operational V/25 0V/ ms or 8 ns, while the output will have changed (8 -- 3 amplifiers, such as TL083, they show better noise × 10 ) only 56 mV.The differential input signal is then (VIN performance, improved output drive capability and -- V O)RI/RI +RF or approximately 1 V. considerably higher small--signal and power bandwidths. The diode limiter will definitely be active and output This makes the devices especially suitable for application distortion will occur; therefore, VIN < 1 V as indicated. in high quality and professional audio equipment, Next, a sine wave input is used with a similar circuit. instrumentation and control circuits, and telephone channel The slew rate of the input waveform now depends on amplifiers. frequency and the exact expression is: The op amps are internally--compensated for gain equal dv 2ω cos ωt to, or higher than, three. The frequency response can be dt = optimized with an external compensation capacitor for The upper limit before slew rate distortion occurs for various applications (unity gain amplifier, capacitive load, small--signal (VIN < 100 mV) conditions is found by setting slew rate, low overshoot, etc.) If very low noise is of prime the slew rate to 7 V/ ms. That is: importance, it is recommended that the 5534A version be 7x106 V ms 2ω cos ωt used which has guaranteed noise specifications. ∕ = at ωt=0 APPLICATIONS 6 7x10 6 ωLIMIT = = 3.5 x 10 rad∕s Diode Protection of Input 2 The input leads of the device are protected from 3.5 x 106 fLIMIT = ≈ 560 kHz differential transients above ±0.6 V by internal 2 π back--to--back diodes (Figure 4). Their presence imposes certain limitations on the amplifier dynamic characteristics related to closed--loop gain and slew rate. dV/dt +2

--

-- 2 V VIN =2Sinωt 1KΩ +

22 pF 1KΩ

+ NE 5534

Figure 4.

Consider the unity gain follower as an example. Assume a signal input square wave with dV/dt of 250 V/ ms and 2 V peak amplitude as shown (Figures 5 Figure 5. and 6). If a 22 pF compensation capacitor is inserted and the

RF

5 22 pF R t -- C 2V C 0 2 8 R1 NE 5534 0 6 -- V O -- V in C1 3 ∆t1 + ∆t2

Figure 6.

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External Compensation Network Improves Bandwidth RF By using an external lead--lag network, the follower 1KΩ circuit slew rate and small--signal bandwidth can be Ri -- increased. This may be useful in situations where a closed--loop gain less than 3 to 5 is indicated. A number of R examples are shown in subsequent figures. The principle LAG NETWORK NE5534 benefit of using the network approach is that the full slew C rate and bandwidth of the device is retained, while + impulse--related parameters such as damping and are controlled by choosing the appropriate circuit constants. For example, consider the following Figure 7. configuration (Figure 7):

GAIN PHASE 90 0

45 θ -- 9 0 o

LAG NETWORKS

0 --180o 00.11.0105000.11.01050 MHz MHz Figure 8. Figure 9.

The major problem to be overcome is poor phase margin leading to instability. 2 -- By choosing the lag network break frequency one decade 6 VOUT below the unity gain crossover frequency (30--50 MHz), the 3 8 phase and gain margin are improved (see Figures 8 and 9). VIN + NOTES 5 An appropriate value for R is 270 Ω. Setting the lag network C =C (1) 1 C C1 break frequency at 5 MHz, C may be calculated: CC = 22 pF for NE5533/34 CC = 22 pF [See graph under typical performance characteristics] 1 C = 2 π ⋅ 270 ⋅ 5x106 Figure 10. Unity Gain Non--Inverting Configuration = 118 pF

Rules and Examples RF

R Compensation Using Pins 5 and 8 (Limited Bandwidth IN 2 VIN -- and Slew Rate) 6 VOUT A single--pole and zero inserted in the transfer function 3 8 will give an added 45° of phase margin, depending on the + network values. 5 C1 Calculating the Lead--Lag Network

1 RIN Figure 11. Unity Gain Inverting Configuration C1 = Let R1 = 2 π F1 R1 10 where F 1 (UGBW) 1 = 10 UGBW = 30 MHz

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External Compensation for Wide--Band CF Voltage--Follower

Shunt Capacitance Compensation RF 1 CF = ,FF ≈ 30MHz 2π FF RF RIN or -- VIN CDIST C1 CF ≈ VOUT ACL CDIST ≈ Distributed Capacitance ≈ 2--3pF R1 Many audio circuits involve carefully--tailored frequency responses. Pre--emphasis is used in all recording mediums to + reduce noise and produce flat frequency response. The most NOTE: often used de--emphasis curves for broadcast and home Input diodes limit differential to <0.5V entertainment systems are shown in Figures 13 through 17 Figure 12. External Compensation for Wideband on the following page. Operational amplifiers are well Voltage Follower suited to these applications because of their high gain and easily--tailored frequency response.

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30 40 TURN OVER FREQUENCIES TURN OVER FREQUENCIES 25 50 Hz, 500 Hz, 2122 Hz 35 50 Hz, 3180 Hz 20 TIME CONSTANTS TIME CONSTANTS 15 3150 ms 30 3150 ms 318 ms 50 ms 10 75 ms 25 5 20 0 -- 5 15 RELATIVE GAIN (dB) RELATIVE GAIN 9dB) -- 1 0 10 -- 1 5 5 -- 2 0 -- 2 5 0 -- 3 0 10 100 1K 10K 100K 10 100 1K 10K 100K FREQUENCY (Hz) FREQUENCY (Hz) Figure 13. RIAA Equalization Figure 14. NAB Standard Playback 71/2 IPS

40 TURN OVER FREQUENCIES 35 50 Hz, 1326 Hz

30 TIME CONSTANTS 3150 ms 125 ms 25

20

15

RELATIVE GAIN (dB) 10

5

0

10 100 1K 10K 100K FREQUENCY (Hz) Figure 15. 3.75 IPS Tape Equalization

25 5 TURN OVER FREQUENCY 2122 CPS TURN OVER FREQUENCY 1 kHz TIME CONSTANT 75 ms 20 0

15 -- 5 10 -- 1 0 5

0 -- 1 5

-- 5 -- 2 0 RELATIVE GAIN (dB)

-- 1 0 RELATIVE GAIN (dB) -- 2 5 -- 1 5 -- 3 0 -- 2 0

-- 2 5 -- 3 5 10 100 1K 10K 100K 10 100 1K 10K 100K FREQUENCY (Hz) FREQUENCY (Hz) Figure 16. Base Treble Curve Figure 17. Standard FM Broadcast Equalization

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RIAA PREAMP USING THE NE5534 Low frequency boost is provided by the inductance of the The preamplifier for phono equalization is shown in magnetic cartridge with the RC network providing the necessary Figure 18 with the theoretical and actual circuit response. break points to approximate the theoretical RIAA curve.

-- 1 5 V

0.22 mF INPUT + NE5534 OUTPUT RSL 1.1 MΩ --

1.1 KΩ -- 1 5 V 20 mF 100 KΩ 1MΩ RIAA NAB

750 pF 0.0033 mF

NOTES: *Select to provide specified transducer loading. 1.1 MΩ Output Noise 0.8mV (with input shorted) ≥ RMS 16 KΩ 0.003 mF

a. 70 70 60 60

50 50 ACTUAL RESPONSE BODE PLOT 40 ACTUAL 40 RESPONSE 30

30 GAIN — dB GAIN — dB 20 20

10 10 0 0 101 102 103 104 105 101 102 103 104 105 FREQUENCY (Hz) FREQUENCY (Hz)

b. Bode Plot of RIAA Equalization and the Response c. Bode Plot of NAB Equalization and the Response Realized in an Actual Circuit Using the 531. Realized in the Actual Circuit Using the 531.

Figure 18. Preamplifier -- RIAA/NAB Compensation

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RUMBLE FILTER Following the amplifier stage, rumble and scratch filters approach and features switchable break points. With the are often used to improve overall quality. Such a filter circuit of Figure 19, any degree of filtering from fairly sharp designed with op amps uses the 2--pole Butterworth to none at all is switch--selectable.

20 KΩ 1

10 KΩ 2 -- -- 6.8 KΩ 3 100 Ω 0.1 mF m 0.1 F NE5534 0.0022 mF NE5534 + 4 +

220 kΩ 1

75 kΩ 2 20 KΩ

47 kΩ 3 10 KΩ 0.0056 mF 27 kΩ 4 6.8 KΩ

39 kΩ

22 kΩ 20 KΩ

13 kΩ 10 KΩ

6.8 KΩ

RUMBLE 6.8 KΩ 330 pF SCRATCH POSITION FREQ. POSITION FREQ. 1 FLAT 1 5kHz 2 30 MHz 2 10 MHz 3 50 Hz 3 15 Hz 4 80 Hz 4 FLAT

Figure 19. Rumble/Scratch Filter

TONE CONTROL Tone control of audio systems involves altering the flat of Figure 20 provides 20 dB of bass or treble boost or cut as response in order to attain more low frequencies or more set by the variable resistance. The actual response of the high ones, dependent upon listener preference. The circuit circuit is shown also.

1 mF 10 KΩ 100 KΩ 10 KΩ +140 MAX MAX INPUT BASS TREBLE +30 BOOST BOOST

+20 0.033 mF0.033mF V+ +10 10 KΩ 0 + OUTPUT A 5V GAIN (dB) -- 1 0 -- PEAK TO PEAK 3.3 KΩ -- 2 0 0.033 mF 0.033 mF 68 KΩ MAX MAX V-- -- 3 0 BASS TREBLE CUT CUT 100 KΩ -- 4 0 10 100 1,000 10,000 100,000 NOTES: 1. Amplifier A may be a NE531 or 301. Frequency compensation, as for unity gain non--inverting amplifiers, must be used. FREQUENCY (Hz) 2. Turn--over frequency -- 1k Hz. 3. Base boost +20 dB, bass cut --20 dB, treble boost +19 dB at 20 Hz, treble cut --19 dB at 20 Hz.

Figure 20. Tone Control Circuit for Operational Amplifiers

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BALANCE AND LOUDNESS AMPLIFIER Figure 21 shows a combination of balance and loudness levels. Balance, level, and loudness controls provide all the controls. Due to the non--linearity of the human hearing listening controls to produce the desired music response. system, the low frequencies must be boosted at low listening

100 KΩ

0.5 mF AIN -- LEVEL 5534 100 KΩ + 220 pF -- 100 KΩ 5534 AOUT 4.7 KΩ 120 Ω LOUDNESS + IN

BALANCE OUT 26 KΩ 1.2 KΩ

4.7 KΩ 0.33 mF 100 KΩ 100 KΩ

0.5 mF

BIN -- 5534 100 KΩ + 220 pF -- 5534 BOUT 1290 Ω + 100 KΩ

1.2 KΩ

0.33 mF 100 KΩ

Figure 21. Balance Amplifier with Loudness Control

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VOLTAGE AND CURRENT OFFSET ADJUSTMENTS Many IC amplifiers include the necessary pin connections Figure 24 provides sufficient current into the input to cancel to provide external offset adjustments. Many times, however, the bias current requirement. Although more simplified it becomes necessary to select a device not possessing arrangements are possible, the addition of Q2 and Q3 provide external adjustments. Figures 22, 23, and 24 suggest some a fixed current level to Q1, thus, bias cancellation can be possible arrangements for off--circuitry. The circuitry of provided without regard to input voltage level.

R3

+V INPUT R3 R4 + R1 200 KΩ R4 NE5534 OUTPUT R5 50 KΩ -- -- OUTPUT R1 NE5534 100 KΩ R5 R2 + 100 Ω 50 KΩ R2 RANGE = V -- V R2 R1 RANGE = V R2 R1 100 Ω INPUT R3 GAIN = 1 + R4 + R2

Figure 23. Universal Offset Null for Non--Inverting Figure 22. Universal Offset Null for Inverting Amplifiers Amplifiers

V+ BIAS CURRENT COMPENSATION

R3 R1

Q3

Q2

R2

Q1 --

NE5534 VOUT V + SELECT R2 AND R3 FOR IN DESIRED CURRENT

V-- Figure 24. Bias Current Compensation

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ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.

PUBLICATION ORDERING INFORMATION LITERATURE FULFILLMENT: N. American Technical Support: 800--282--9855 Toll Free ON Semiconductor Website: http://onsemi.com Literature Distribution Center for ON Semiconductor USA/Canada P.O. Box 61312, Phoenix, Arizona 85082--1312 USA Order Literature: http://www.onsemi.com/litorder Phone: 480--829--7710 or 800--344--3860 Toll Free USA/Canada Japan: ON Semiconductor, Japan Customer Focus Center Fax: 480--829--7709 or 800--344--3867 Toll Free USA/Canada 2--9--1 Kamimeguro, Meguro--ku, Tokyo, Japan 153--0051 For additional information, please contact your Email: [email protected] Phone: 81--3--5773--3850 local Sales Representative. http://onsemi.com AND8177/D 11