A Collection of Definitions and Fundamentals for a Design-Oriented
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A collection of definitions and fundamentals for a design-oriented inductor model 1st Andr´es Vazquez Sieber 2nd M´onica Romero * Departamento de Electronica´ * Departamento de Electronica´ Facultad de Ciencias Exactas, Ingenier´ıa y Agrimensura Facultad de Ciencias Exactas, Ingenier´ıa y Agrimensura Universidad Nacional de Rosario (UNR) Universidad Nacional de Rosario (UNR) ** Grupo Simulacion´ y Control de Sistemas F´ısicos ** Grupo Simulacion´ y Control de Sistemas F´ısicos CIFASIS-CONICET-UNR CIFASIS-CONICET-UNR Rosario, Argentina Rosario, Argentina [email protected] [email protected] Abstract—This paper defines and develops useful concepts related to the several kinds of inductances employed in any com- prehensive design-oriented ferrite-based inductor model, which is required to properly design and control high-frequency operated electronic power converters. It is also shown how to extract the necessary parameters from a ferrite material datasheet in order to get inductor models useful for a wide range of core temperatures and magnetic induction levels. Index Terms—magnetic circuit, ferrite core, major magnetic loop, minor magnetic loop, reversible inductance, amplitude inductance I. INTRODUCTION Errite-core based low-frequency-current biased inductors F are commonly found, for example, in the LC output filter of voltage source inverters (VSI) or step-down DC/DC con- verters. Those inductors have to effectively filter a relatively Fig. 1. General magnetic circuit low-amplitude high-frequency current being superimposed on a relatively large-amplitude low-frequency current. It is of practitioner. A design-oriented inductor model can be based paramount importance to design these inductors in a way that on the core magnetic model described in this paper which a minimum inductance value is always ensured which allows allows to employ the concepts of reversible inductance Lrevˆ , the accurate control and the safe operation of the electronic amplitude inductance La and initial inductance Li, to further power converter. In order to efficiently design that specific type develop an optimized inductor design method. Those induc- of inductor, a method to find the required minimum number tance definitions rely on their respective core permeabilities, of turns Nmin and the optimum air gap length gopt to obtain a which in this paper are also revisited, contextualized and specified inductance at a certain current level is needed. This obtained for two specific ferrite materials: TDK-EPCOS N27 method has to be based upon an accurate inductor model, for and TDK-EPCOS N87. which certain inductances and properties need to be defined This paper is organized as follows. In section II, a general arXiv:2008.13634v3 [physics.app-ph] 20 Oct 2020 and explained. Also, these inductance definitions needs to be magnetic core model is described and its associated perme- parametrized, among other things, according to the specific abilities are introduced. In section III, definitions of several ferrite material employed in the core. types of inductances are presented. Section IV shows how to The problem of designing such kind of inductors has been obtain the previously defined permeabilities from the ferrite widely treated in literature [1], [2], [3], [4]. At the same material datasheet. Section V presents some useful properties time, there are many well established definitions of core of the reversible inductance that could be needed to justify the permeability and inductance [4], [5], [11] according to the selection criterion of the inductance value as well as Nmin and actual inductor operating condition. However, it seems that gopt. Finally, conclusions are presented in section VI. this variety of inductance definitions can be better exploited in order to enhance the inductor design process. In this II. MAGNETIC CIRCUIT MODEL paper, some specific inductance definitions are revisited and In this section, we obtain a model for the general magnetic presented under a suitable context for the power electronic circuit considered in Figure 1 using an approach depending on integration along the mean magnetic path into the ferrite core, Lc and into the air gap, Lg [5]. Suppose that current i(t) can be easily decomposed into a) a component denoted as iLF (t) at a relatively low frequency fLF and b) a component denoted as iHF (t) at a relatively high frequency fHF , with fLF ≪ fHF . At a certain time tˆLF , iLF reaches its peak value ˆiLF and then we have 1 1 i(t) ≈ ˆiLF + iHF (t) t ∈ tˆLF − , tˆLF + (1) fHF fHF In such a situation, Ampere’s law relates the frequency com- ponents of current i(t) with their corresponding magnetic field strength H components as follows H~ (t,l)dl~ = HˆLF (l)+ HHF (t,l) dl ∪ I ZLc Lg h i = N ˆiLF + iHF (t) h i where dl~ is the path vector, parallel to H~ . Separating the frequency components yields ˆ ˆ ˆ HLF (l)dl + HLF (l)dl = NiLF (2) Fig. 2. Ferrite magnetization curve ZLc ZLg HHF (t,l)dl + HHF (t,l)dl = NiHF (t) Z Z Lc Lg For any of the points pertaining to that LF-commutation curve, the LF-amplitude permeability µLF is defined as ∆HHF (l)dl + ∆HHF (l)dl = N∆iHF (3) a ZLc ZLg 1 Bˆ where ∆HHF is the amplitude of the field strength excursion µLF Bˆ , ∆B = LF a LF HF ˆ due to ∆iHF , the amplitude of the high-frequency current µ0 HLF ∆BHF excursion during 1 . fHF The magnetic induction B(t,l) = BˆLF (l) + BHF (t,l) because it relates only the low frequency amplitude of the and its peak-to-peak variation ∆BHF determine the peak magnetic induction and field strength in the ferrite material ∆BHF (l) induction Bˆ(l)= BˆLF (l)+ . These are related to their when the low frequency iLF takes also its amplitude value 2 ˆ corresponding field strength Hˆ (l), H (t,l), ∆H (l) iLF . The magnetic induction generated by iLF will not vary LF HF HF ˆ and Hˆ (l) according to the medium permeability. Having the much from BLF while t is into the time span defined in (1). 1 Hence during , iHF (t) will produce an approximately air gap paramagnetic properties, along Lg simply hold fHF closed minor magnetic loop of amplitude (∆BHF , ∆HHF ) BˆLF (l) BHF (t,l) ∆BHF (l) Bˆ(l) starting and ending in the neighbourhood of Bˆ , as it is = = = = µ (4) LF ˆ ˆ 0 HLF (l) HHF (t,l) ∆HHF (l) H(l) shown in Figure 2. The incremental permeability µ∆ˆ at that quasi-static induction level BˆLF is then defined as where µ0 is the vacuum permeability. In the magnetic core path Lc, those relationships depend on the shape of the ferrite ˆ 1 ∆BHF magnetization curve which is shown in Figure 2. It is also µ∆ˆ BLF , ∆BHF = µ0 ∆HHF ˆ the specific major loop that characterizes the behaviour of the BLF ferrite when its magnetic induction evolution spans the two Consequently, on Lc holds extreme points ±Bs, being Bs the saturation induction. In any inductor, although this situation can be reached with a current BˆLF (l) iLF having a sufficiently high ˆiLF , the actual ˆiLF has to be set HˆLF (l)= (5) LF ˆ well below that value since beyond that induction level the core µ0µa BLF , ∆BHF ferrimagnetic properties become severely affected. Starting ∆BHF (l) from a demagnetized core, as ˆi is gradually increased ∆HHF (l)= (6) LF ˆ from zero towards the maximum value causing saturation, µ0µ∆ˆ BLF , ∆BHF the tipping points (BˆLF ,HˆLF and −BˆLF ,−HˆLF ) of the ever increasing LF-major loops describe a LF-commutation curve If ∆BHF is made sufficiently small, then µ∆ˆ and the which is also partly shaped by the current magnitude of LF-commutation curve start to be practically independent of ∆BHF , due to the memory properties of the ferrite material. ∆BHF . At this point, on the one hand the existing linear relationship between BHF and HHF is captured by the so- The peak linkage flux Ψˆ and magnetic induction Bˆ(l) in the called reversible permeability at BˆLF , µrevˆ ferrite core are ∆ΨHF µrev BˆLF = lim µ BˆLF , ∆BHF ˆ ˆ ˆ → ∆ˆ Ψ= ΨLF + (11) ∆BHF 0 2 On the other hand, the LF-commutation curve tends to the Ψˆ Bˆ(l)= regular commutation curve and their respective amplitude NAc(l) permeabilities are related as III. INDUCTANCE DEFINITIONS ˆ ˆ 1 B LF ˆ µa B = = lim µa BLF , ∆BHF Combining (2), (3), (4), (5), (8), (9) and (10) yield the LF- µ0 Hˆ BˆLF →Bˆ LF amplitude inductance, La and the incremental inductance, ∆BHF →0 L∆ˆ = µa BˆLF Ψˆ LLF ˆ , LF Now making BˆLF → 0 due to ˆiLF → 0, the initial a ΨLF ∆ΨHF = ˆiLF permeability µi is defined as ∆ΨHF 2 N µi = lim µa BˆLF = µrevˆ BˆLF =0 = (12) LF BˆLF →0 R ˆ R ca ΨLF , ∆ΨHF + g Note that in the core, the relationship between B and H ˆ ∆ΨHF depends not only on the ferrite magnetic characteristics but L∆ˆ ΨLF , ∆ΨHF = ∆iHF ˆ also on the way in which B evolves with time. ΨLF N 2 In the magnetic circuit of Figure 1, a closed surface = (13) S = Sc ∪ Sg that intersects both Lc and Lg paths will satisfy ˆ Rc∆ˆ ΨLF , ∆ΨHF + Rg according to Gauss’ law that with B~ (t,l)dS~ = B~ (t,l)dS~ (7) LF dl ZZSc ZZSg R ˆ ca ΨLF , ∆ΨHF = LF Ψˆ LF ∆ΨHF ZLc µ µ , Ac(l) where Sc is a core cross-section perpendicular to Lc, Sg is 0 a NAc NAc the remaining surface of S crossing the air gap and dS~ is the (14) area vector of S. The left side of (7) is the core magnetic flux ˆ dl Rc ˆ ΨLF , ∆ΨHF = Φc since the magnetic induction there is mainly concentrated ∆ ˆ ZL ΨLF ∆ΨHF c µ0µ∆ˆ NA , NA Ac(l) into Sc because µa,µ ˆ ≫ 1.