DOCSLIB.ORG

2B1Q, 142–143 4B3T Modified Monitored State

Total Page：16

File Type：pdf, Size：1020Kb

Download full-text PDF Read full-text
2B1Q, 142–143 4B3T Modified Monitored State Derickson.book Page 911 Thursday, November 8, 2007 11:11 AM Index 2B1Q, 142–143 optical sampling demonstrations, 427 4B3T modified monitored state (MMS43), optical waveform measurement techniques, 423 142–143 optical waveform sampling, 423–426 4B5B block substitution, 70–74 See also All-optical sampling implementations, 4B5B encoder efficiency, 89 experimental; Fiber FWM-based sampling 8B10B system, performance analysis of; Optical block substitution, 74–77 sampling principles; Sampling gate control words, 154, 162 implementations; Third-order nonlinearity- encoder efficiency, 89 based sampling; Timebase designs encoding rules, 862–872 All-optical sampling implementations, 10GBase control codes, 157 experimental 10GBase stress testing, 619–628 analog-to-digital conversion of acquired 10GBase-KR, 642, 651–654 samples, 480–482 10GBase-LR, 619 χ2-based sampling in bulk KTP, 482–484 10GBase-LRM, 634 χ2-based sampling using quasi-phase matching 64B66B encoder in PPLN, 484–486 code blocks, 160 χ3-based Kerr switch with parametric gain in control characters, 157 HNLF, 487–488 deserializer architecture, 158 χ3-based sampling system using XPM-induced frame structure, 161 frequency shift in HNLF, 486–487 scrambler, 162–163 coherent detection sampling (linear sampling), serializer architecture, 158 489–491 fiber FWM-based sampling in HNLF, 488–489 A gain-transparent ultrafast nonlinear interferometer, 489–490 Accelerated BER measurements, 192 optimization for 40 Gbit/s signals, 491–492 Active bias T, 122–123, 902–910 sampling pulse sources, 475–480 Add/drop multiplexers (ADMs), 590 selected implementations, 482–492 Adjustable offset amplifiers, 552 All-zero state, 821–823, 827 ADSL (Asymmetric DSL), 140, 144–145 Alternate mark inverted (AMI) encoding rule, Aggregate deterministic jitter, 403 97–99 Aggregate total jitter, 403–404 Amplification, 384 Aliasing, 258, 262, 298–299, 480, 640 clock phase noise, 40 All-optical sampling for high-speed waveform parametric amplification, 436, 488 analysis variable gain preamplifier, 245–246 electronic sampling, comparison with, 422–423 See also Preemphasis 911 Derickson.book Page 912 Thursday, November 8, 2007 11:11 AM 912 Index Amplified spontaneous emission (ASE), 486, 581, Attenuators 607–613, 616–617 fixed step, 836–837 Amplifiers optical, 567–569, 636 buffer, 123, 880, 908–910 variable optical, 131–138 error, 66, 511–512, 516–521, 873–875 Autocorrelation, 423, 450, 825–826 optical, 362, 578, 581, 609–610, 617 Automatic mask testing, 364–365 power, 122–123 Avalanche photodetectors (APDs), 424, 457, 464, See also Erbium-doped fiber amplifiers 492, 564, 572, 623–624 (EDFAs); Semiconductor optical amplifiers Average optical power, 619–623 (SOAs); Transimpedance amplifiers (TIAs) Averaging AM-to-PM conversion, 115 in configuration of network analyzer hardware, Analog CDR circuits, 11 727 Analog phase detection, 512–513 magnitude spectra, 296 Analog receiver characteristics, estimating noise, 473 digitally, 585–588 reducing noise impact on eye diagrams, 345–346 Analog-to-digital conversion (ADC) of acquired See also Trace averaging samples, 480–482 Analog-to-digital converters (ADC), 92–95, 98, 245 B Analog-to-digital sampling, 92–94 Analysis methods (approaches) B8ZS encoding, 99 comparison for DDJ and DCD, 293–295 Backplane, 172, 175, 606 comparison for PJ, 296–299 communication, 642, 651–654 pattern-correlation-based for DDJ and DCD, test sytem, 702–703 291–293 See also Backplane modeling residual for PJ extraction, 296 Backplane modeling spectrum analysis for composite jitter, 300–302 daughtercards assembly, 703 spectrum analysis for PJ extraction, 295–296 eye diagrams, 708–709 spectrum analysis for RJ extraction, 283–289 impedance values, 706 spectrum-based for DDJ and DCD, 289–291 SPICE simulation, 705 tail-fit for RJ extraction, 286–289 topological model, 702 Analysis of waveforms, 350–353 waveforms, 703–704 APDs. See Avalanche photodetectors (APDs) Ball grid array (BGA), 696–697 Arbitrary waveform generators (AWGs), 547–549 Band-pass filters Architecture insertion loss, 768–770 FBDIMM, 795–797, 804–806 measurements summary, 770–771 forwarded clock systems, 816 receivers based on, 720 network analyzers, 716–719 return loss, 767–768 PCI Express, 789–795, 800–804 Band-pass response, 98, 112–114, 880–902 real-time oscilloscopes, 245–250 Bandwidth sampling oscilloscopes, 335 cost of, 332 SATA, 797–800, 807–810 effect on waveform results, 353–358 ARCNET, 87–88 front-end, 256–257 Asymmetric crosstalk, 144 full width at half maximum (FWHM), 613 Atomic clocks, 106 and ISI, 40 Attenuation, 26, 616, 633, 653 limitations, 40 ratios, 836–837 relationship equations, 303, 331–332 See also Deemphasis sample rates, 331–335 Derickson.book Page 913 Thursday, November 8, 2007 11:11 AM Index 913 Bang-bang phase detectors, 513–514 loopback configurations, 174 Barkhausen criteria, 506 mean time between errors (MTBE), 171 Baseline wander, 13, 15, 108–113, 845–846 pattern generator (PG), 171–173 Bathtub curve, 325 receiver setup, 175–176 linear scale, 202–203 sampling rate, 266 logarithmic scale, 203 SERDES devices, 172–174 Q scale, 203–205 setup, 171–174 Behavioral modeling, 695–696 synchronization, 176–177 BER (bit error ratio), 170–171, 222–225 system bit error ratio, 193 confidence intervals for, 583 target bit error ratio, 177–178 level in RJ/DJ separation settings, 313 test pattern selection, 174–175 BER calculations in real communications systems testing in Ethernet, 597–602 BERT testing in Ethernet, 597–602 BERT scan measurements frame error ratio, estimating, 599–600 base bit error ratio, 222–225 frame-by-frame testing, advanced, 600–601 bathtub curve, 202–205 frame-by-frame testing, simple, 598–599 BERT eye masks, 237–238 sequencing, 602 bit error ratio eye diagram, 229–233 SONET/SDH, analyzing BER measurements contour plots, 231–232 in, 592–596 fast total jitter optimization, 219–222 SONET/SDH description, 589–592 full eye scan, 228–238 BER eye diagram gradient maps, 233–234 contour plots, 231–232 jitter histogram, 205–206 pseudo-color plots, 229–230 logarithmic scale, 203 three-dimensional plots, 232 low-frequency jitter, 225–226 BER measurements in Ethernet measurement procedure, 213–215 BERT testing, 597–602 median filter, 206 frame error ratio, estimating, 599–600 number of errors optimization, 218–219, 222 frame-by-frame testing, advanced, 600–601 periodic jitter level, 207–210 frame-by-frame testing, simple, 598–599 phase margin, 210 sequencing, 602 pseudo-color plots, 229–230 BER measurements in SONET/SDH Q factor method, 210–213 analysis of, 592–596 random jitter level, 207 SONET/SDH description, 589–592 sample delay scan, 200–226 BER tests and signaling for chip-to-chip link sample point optimization, 215–218 systems sample threshold scan, 226–228 FBDIMM architecture and testing, 804–806 scope-like eye diagram, 233–234 JNB testing for multiple-Gb/s standards, 810 spectral jitter decomposition, 238–241 PCI Express architecture and testing, 800–804 successive refinement algorithms, 237 SATA architecture and testing, 806–810 three-dimensional plots, 232 BER vs. OSNR, 609–618 total jitter, 210 Berlekamp-Massey algorithm, 823 Bessel filter design, 369–371 BERT (bit error ratio testing) Bessel null measurement method, 553–555 accelerated BER measurements, 192 Bessel-shaped receiver, 481 band-pass response, 112–113 Bessel-Thomson (BT) filter, 625, 638–639, BER statistics, 178–192 646–648, 843–844 bit error rate, 171 Bessel-Thomson reference receiver, 268 definitions, 170–171 Bias networks, 85, 112, 122–123, 886, 892, error detector (ED), 171–174 900–901 Derickson.book Page 914 Thursday, November 8, 2007 11:11 AM 914 Index Bias Ts, 121–123, 845–846, 902–910 χ3-based sampling using XPM-induced frequency Bimodal digital data signal, 200–201 shift in HNLF, 486–487 Binary data properties, 13 Cables Binary line codes, 14–20 coaxial cable standards, 857 Binary-to-ternary conversion, 98 matching, 775–777 BIP (binary interleaved parity) codes, 592–596 phase matching of, 773–775 Bipolar return-to-zero (BPRZ) code, 20 See also Coaxial cables Birefringent phase matching, 428–430, 443 Calibration in jitter tolerance testing Bit error rate, 171 description, 553 Bit error ratio (BER). See BER (bit error ratio) J1/J0 measurement method, 555 Bit error ratio testing (BERTs). See BERT (bit measuring SJ with spectrum analyzer, 553–555 error ratio testing) Calibration options in frequency domain Bit labels, 264 measurements Bit periods, 31–33, 196 calibration process, 749 Bit stuffing, 97, 102, 104 one-port calibration, 747–748 Black box models, 695–696 response calibration, 747 Blackman-Harris window, 283 two-port calibration, 748 Block codes, 22–23 CAN (Controller Area Network), 88 BNC connectors, 858 Capacitance Bondwire, 659–660, 668 coaxial structures, 848–849 Bounded uncorrelated jitter (BUJ), 289, 320–321, fringing, 676 550 lossless transmission line, 659 Bounding box, 234–235 parasitic, 111–112, 564, 873, 880, 885, 890, BRI (Basic Rate Interface), 142, 144 899–901 Brownian noise, 281 power plane, 124 Buffer amplifier, 123, 880, 908–910 susceptance, 854–855 BUJ (bounded uncorrelated jitter), 289, 320–321, Capacitive discontinuity, 673, 692 550 Capacitive termination, 669–670 Bulk crystal length, optimum, 443–444 Capacitor coupling network, 107–108, 110–113 Bulk KTP, χ2-based sampling in, 482–484 Capturing waveform records, 262 Bulk nonlinear crystals, χ2-based gates in, Carrier sense multiple access collision detect 443–444 (CSMACD), 68, 150, 862n, 871n Butterworth filters, 256, 324, 843–844 Carrierless Amplitude
Load more

Recommended publications
  • Digital Transmission 01204325 Data Communications and Computer Networks
    Digital Transmission 01204325 Data Communications and Computer Networks Chaiporn Jaikaeo Department of Computer Engineering Kasetsart University Based on lecture materials from Data Communications and Networking, 5th ed., Behrouz A. Forouzan, McGraw Hill, 2012. Revised 2021-05-07 Outline • Line coding • Encoding considerations • DC components in signals • Synchronization • Various line coding methods • Analog to digital conversion 2 Line Coding • Process of converting binary data to digital signal 3 Signal vs. Data Elements 1 data element = 1 symbol 4 Encoding Considerations • Signal spectrum ◦ Lack of DC components ◦ Lack of high frequency components • Clocking/synchronization • Error detection • Noise immunity • Cost and complexity 5 DC Components • DC components in signals are not desirable ◦ Cannot pass thru certain devices ◦ Leave extra (useless) energy on the line ◦ Voltage built up due to stray capacitance in long cables v Signal with t DC component v Signal without t DC component 6 Synchronization • To correctly decode a signal, receiver and sender must agree on bit interval 0 1 0 0 1 1 0 1 Sender sends: v 01001101 t 0 1 0 0 0 1 1 0 1 1 Receiver sees: v 0100011011 t 7 Providing Synchronization • Separate clock wire Sender data Receiver clock • Self-synchronization 0 1 0 0 1 1 0 1 v t 8 Line Coding Methods • Unipolar ◦ Uses only one voltage level (one side of time axis) • Polar ◦ Uses two voltage levels (negative and positive) ◦ E.g., NRZ, RZ, Manchester, Differential Manchester • Bipolar ◦ Uses three voltage levels (+, 0, and
    [Show full text]
  • Criteria for Choosing Line Codes in Data Communication
    ISTANBUL UNIVERSITY – YEAR : 2003 (843-857) JOURNAL OF ELECTRICAL & ELECTRONICS ENGINEERING VOLUME : 3 NUMBER : 2 CRITERIA FOR CHOOSING LINE CODES IN DATA COMMUNICATION Demir Öner Istanbul University, Engineering Faculty, Electrical and Electronics Engineering Department Avcılar, 34850, İstanbul, Turkey E-mail: [email protected] ABSTRACT In this paper, line codes used in data communication are investigated. The need for the line codes is emphasized, classification of line codes is presented, coding techniques of widely used line codes are explained with their advantages and disadvantages and criteria for chosing a line code are given. Keywords: Line codes, correlative coding, criteria for chosing line codes.. coding is either performed just before the 1. INTRODUCTION modulation or it is combined with the modulation process. The place of line coding in High-voltage-high-power pulse current The transmission systems is shown in Figure 1. purpose of applying line coding to digital signals before transmission is to reduce the undesirable The line coder at the transmitter and the effects of transmission medium such as noise, corresponding decoder at the receiver must attenuation, distortion and interference and to operate at the transmitted symbol rate. For this ensure reliable transmission by putting the signal reason, epecially for high-speed systems, a into a form that is suitable for the properties of reasonably simple design is usually essential. the transmission medium. For example, a sampled and quantized signal is not in a suitable form for transmission. Such a signal can be put 2. ISSUES TO BE CONSIDERED IN into a more suitable form by coding the LINE CODING quantized samples.
    [Show full text]
  • Multilevel Sequences and Line Codes
    COPYRIGHT AND CITATION CONSIDERATIONS FOR THIS THESIS/ DISSERTATION o Attribution — You must give appropriate credit, provide a link to the license, and indicate if changes were made. You may do so in any reasonable manner, but not in any way that suggests the licensor endorses you or your use. o NonCommercial — You may not use the material for commercial purposes. o ShareAlike — If you remix, transform, or build upon the material, you must distribute your contributions under the same license as the original. How to cite this thesis Surname, Initial(s). (2012) Title of the thesis or dissertation. PhD. (Chemistry)/ M.Sc. (Physics)/ M.A. (Philosophy)/M.Com. (Finance) etc. [Unpublished]: University of Johannesburg. Retrieved from: https://ujdigispace.uj.ac.za (Accessed: Date). MULTILEVEL SEQUENCES AND LINE CODES by LOUIS BOTHA Thesis submitted as partial fulfilment of the requirements for the degree MASTER OF ENGINEERING in ELECTRICAL AND ELECTRONIC ENGINEERING in the FACULTY OF ENGINEERING at the RAND AFRIKAANS UNIVERSITY SUPERVISOR: PROF HC FERREIRA MAY 1991 SUMMARY As the demand for high-speed data communications over conventional channels such as coaxial cables and twisted pairs grows, it becomes neccesary to optimize every aspect of the communication system at reasonable cost to meet this demand effectively. The choice of a line code is one of the most important aspects in the design of a communications system, as the line code determines the complexity, and thus also the cost, of several circuits in the system. It has become known in recent years that a multilevel line code is preferable to a binary code in cases where high-speed communications are desired.
    [Show full text]
  • CODING for Transmission
    CODING for Transmission Professor Izzat Darwazeh Head of Communicaons and Informaon System Group University College London [email protected] Acknowledgement: Dr A. Chorti, Princeton University for slides on FEC coding Dr P.Moreira, CERN, for slides on the CERN Gigabit Transmitter (GBT) Dr J. Mitchell, UCL, for the sampled music and voice. June 2011 Coding • Defini7ons and basic concepts • Source coding • Line coding • Error control coding Digital Line System Message Message source Distortion, sink interference Input Output signal and noise signal Encoder- Demodulator modulator -decoder Communication Transmitted channel Received signal signal Claude Shannon • Shannon’s Theorem predicts reliable communicaon in the presence of noise “Given a discrete, memoryless channel with capacity C, and a source with a posi8ve rate R (R<C), there exist a code such that the output of the source can be transmi@ed over the channel with an arbitrarily small probability of error.” • B is the channel bandwidth in Hz and S/N is the signal power to noise power rao ⎛⎞S CBc =+log2 ⎜⎟ 1 ⎝⎠N Types of Coding • Source Coding – Encoding the raw data • Line (or channel) Coding – Formang of the data stream to benefit transmission • Error Detec7on Coding – Detec7on of errors in the data seQuence • Error Correcon Coding – Detec7on and Correc7on of Errors • Spread Spectrum Coding – Used for wireless communicaons Signals and sources: Discrete - Con8nuous m(t) n Continuous Time and Amplitude n Discrete Time, continuous Amplitude – PAM signal n Discrete Time, and Amplitude
    [Show full text]
  • Spectral Management on Metallic Access Networks; Part 1: Definitions and Signal Library 2 ETSI TR 101 830-1 V1.2.1 (2001-08)
    ETSI TR 101 830-1 V1.2.1 (2001-08) Technical Report Transmission and Multiplexing (TM); Access networks; Spectral management on metallic access networks; Part 1: Definitions and signal library 2 ETSI TR 101 830-1 V1.2.1 (2001-08) Reference RTR/TM-06020-1 Keywords spectral management, unbundling, access, network, local loop, transmission, modem, POTS, IDSN, ADSL, HDSL, SDSL, VDSL, xDSL ETSI 650 Route des Lucioles F-06921 Sophia Antipolis Cedex - FRANCE Tel.:+33492944200 Fax:+33493654716 Siret N° 348 623 562 00017 - NAF 742 C Association à but non lucratif enregistrée à la Sous-Préfecture de Grasse (06) N° 7803/88 Important notice Individual copies of the present document can be downloaded from: http://www.etsi.org The present document may be made available in more than one electronic version or in print. In any case of existing or perceived difference in contents between such versions, the reference version is the Portable Document Format (PDF). In case of dispute, the reference shall be the printing on ETSI printers of the PDF version kept on a specific network drive within ETSI Secretariat. Users of the present document should be aware that the document may be subject to revision or change of status. Information on the current status of this and other ETSI documents is available at http://www.etsi.org/tb/status/ If you find errors in the present document, send your comment to: [email protected] Copyright Notification No part may be reproduced except as authorized by written permission. The copyright and the foregoing restriction extend to reproduction in all media.
    [Show full text]
  • ETRI PHY Proposal on VLC Line Code for Illumination
    September 2009 doc.: IEEE 802.15-09-0675-00-0007 Project: IEEE P802.15 Working Group for Wireless Personal Area Networks (WPANs) Submission Title: [ETRI PHY Proposal on VLC Line Code for Illumination] Date Submitted: [23 September, 2009] Source: [Dae Ho Kim, Tae-Gyu Kang, Sang-Kyu Lim, Ill Soon Jang, Dong Won Han] Company [ETRI] Address [138 Gajeongno, Yuseong-gu, Daejeon, 305-700] Voice:[+82-42-860-5648], FAX: [+82-42-860-5218], E-Mail:[[email protected]] Re: [Response to call for proposals] Abstract: [This document describes a proposal of PHY line code for LED illumination ] Purpose: [Proposal to IEEE 802.15.7 VLC TG]] Notice: This document has been prepared to assist the IEEE P802.15. It is offered as a basis for discussion and is not binding on the contributing individual(s) or organization(s). The material in this document is subject to change in form and content after further study. The contributor(s) reserve(s) the right to add, amend or withdraw material contained herein. Release: The contributor acknowledges and accepts that this contribution becomes the property of IEEE and may be made publicly available by P802.15. TG VLC Submission Slide 1 Dae-Ho Kim, ETRI September 2009 doc.: IEEE 802.15-09-0675-00-0007 ETRI PHY Proposal on VLC Line code for Illumination Dae Ho Kim [email protected] ETRI TG VLC Submission Slide 2 Dae-Ho Kim, ETRI September 2009 doc.: IEEE 802.15-09-0675-00-0007 Contents • ETRI PHY Considerations and Scope • Summary of ETRI PHY Proposal • Flickering issue at LED illumination • Proposed Line Code – Modified-4B5B
    [Show full text]
  • Modulation  Copper Access Technologies  Wireless Subscriber Line  Cable Television
    Dr. Beinschróth József Telecommunication informatics I. Part 2 ÓE-KVK Budapest, 2019. Dr. Beinschróth József: : Telecommunication informatics I. Content Network architectures: collection of recommendations The Physical Layer: transporting bits The Data Link Layer: Logical Link Control and Media Access Control Examles for technologies based on the Data Link Layer The Network Layer 1: functions and protocols The Network Layer 2: routing Examle for technology based on the Network Layer The Transport Layer The Application Layer Criptography IPSec, VPN and border protection QoS and multimedia Additional chapters Dr. Beinschróth József: : Telecommunication informatics I. 2 Content of this chapter (1) Network models Theory Media for Data Transmission Twisted Pair Coaxial cable and optical fiber Wireless Data transmission Network topology PSTN Data Transmission Main Parameters of the Physical Layer Mechanical and electrical parameters Functional parameters Approaching from the physical layer Baseband transmission Bitflow (stream) transmission with modulation Copper access technologies Wireless subscriber line Cable Television Dr. Beinschróth József: : Telecommunication informatics I. 3 The physical layer: The lowest layer of the OSI model OSI TCP/IP Hybrid Application Layer Presentation Layer Application Layer Application Layer Session Layer Transport Layer Transport Layer Transport Layer Network Layer Network Layer Network Layer Data Link Layer Data Link Layer Physical Layer Physical Layer Physical Layer Network
    [Show full text]
  • IEEE802.3Z Gigabit Ethernet UTP5 Proposal V2.0 November, 1996
    IEEE802.3z Gigabit Ethernet UTP5 Proposal V2.0 Project: IEEE 802.3z Gigabit Ethernet Task Force Source: Steve Dabecki ([email protected]) Barry Hagglund ([email protected]) Richard Cam ([email protected]) Vern Little ([email protected]) Iain Verigin ([email protected]) PMC-Sierra Inc 105-8555 Baxter Place Burnaby BC Canada V5A 4V7 Tel: 604.415.6000 Web: http://www.pmc-sierra.com Title: Physical Layer Proposal for 1 Gbit/s Full / Half Duplex Ethernet Transmission over Single (4-pair) or Dual (8-pair) UTP-5 Cable. Issue: 2.0 Date: November 11-14, 1996 Abstract The extension of the current IEEE802.3 specifications to support a bit rate of 1Gbps is currently under investigation by the HSSG. These bit rates are regarded to be essential to support the high bandwidth requirements of mixed 10BASE and 100BASE networks, and many applications requiring a dedicated high speed link to a server. The HSSG has already made excellent progress in the way of defining 1000BASE for fibre. This contribution outlines an approach for supporting 1Gbps, either half or full- duplex, over single (4-pair) or dual (8-pair) unshielded twisted pair category 5 (UTP-5) cable. Notice This contribution has been prepared to assist the IEEE802.3z HSSG. This document is offered to the IEEE802.3z HSSG as a basis for discussion and is not a binding proposal on PMC-Sierra, Inc. or any other company. The statements are subject to change in form and/or content after further study. Specifically, PMC-Sierra, Inc.
    [Show full text]
  • Digital Data Transmission Unit 3
    Unit 3 Digital Data Transmission What is Line Coding? The input to a digital system is in the form of sequence of digits. The input can be from the sources such as data set, computer, digitized voice (PCM), digitalTV orTelemetry equipment. Line coding is the process in which the digital input is coded into electrical pulses or waveforms for the transmission over channel. Regenerative Repeaters are used at regular intervals along a digital transmission line to detect the incoming digital signal and to transmit the new clean pulse for the further transmission along the line. Line Coding Line Coding There are many ways of assigning pulses (waveforms) to the digital data. For example a high voltage level (+V) could represent a “1” and a low voltage level (0 or -V) could represent a “0”. Line Coding-Examples Line Coding Signal element versus Data element Data element (1s & 0s) are what we need to send and signal elements (+V & -V voltages) are what we can send. Data elements are being carried and signal elements are the carriers. The data rate defines the number of bits sent per sec - bps. It is often referred to the bit rate. The signal rate is the number of signal elements sent in a second and is measured in bauds. Line Coding Line Coding Requirements Small transmission bandwidth Power efficiency: as small as possible for required data rate and error probability Error detection/correction Timing information: clock must be extracted from data Transparency: all possible binary sequences can be transmitted. LINE CODING Unipolar NRZ All signal levels are on one side of the time axis - either above or below.
    [Show full text]
  • T7264 U-Interface 2B1Q Transceiver
    查询T7264供应商 捷多邦，专业PCB打样工厂，24小时加急出货 Data Sheet April 1998 T7264 U-Interface 2B1Q Transceiver Features — Sigma-delta A/D converter — Internal 15.36 MHz crystal oscillator ■ U-interface 2B1Q transceiver — Supports 15.36 MHz external clock input — Range over 18 kft on 26 AWG ■ Digital signal processor — ISDN basic-rate 2B+D — Digital timing recovery (pull range ±250 ppm) — Full-duplex, 2-wire operation — Echo cancellation (linear and nonlinear) — 2B1Q four-level line code — Accommodates distortion from bridged taps — Conforms to ANSI North American Standard — Scrambling/descrambling T1.601-1992 — crc calculations — Supports NT quiet mode and insertion loss test — Selectable LT or NT operation mode for maintenance — Start-up sequencing with timers ■ K2 interface — Activation/deactivation support — 2B+D data — Cold start in 3.5 seconds (typical) — 512 kbits/s TDM interface — Warm start in 200 ms (typical) — Frame and superframe markers — U-frame formatting and decoding — Embedded operations channel (eoc) — U-interface M bits and crc results — Device control and status Description ■ Other The Lucent Technologies Microelectronics Group ± — Single +5 V ( 5%) supply T7264 U-Interface 2B1Q Transceiver integrated cir- ° ° — –40 C to +85 C cuit provides full-duplex, basic-rate (2B+D) integrated — 44-pin PLCC services digital network (ISDN) communications on a ■ Power consumption 2-wire digital subscriber loop at either the LT or NT — Operating 275 mW typical and conforms to the ANSI North American Standard — Idle mode 30 mW typical T1.601-1992. The single +5 V CMOS device is pack- aged in a 44-pin plastic leaded chip carrier (PLCC). ■ Analog front end — On-chip line driver for 2.5 V pulses — On-chip balance network K2 BUS SCRAMBLER 2B1Q ENCODER K2 FORMAT, DECODE 2-WIRE LINE SIGNAL ECHO 2B1Q DRIVER DETECT CANCELER U-INTERFACE DESCRAM.
    [Show full text]
  • Optical Modulation for High Bit Rate Transport Technologies by Ildefonso M
    Technology Note Optical Modulation for High Bit Rate Transport Technologies By Ildefonso M. Polo I October, 2009 Scope There are plenty of highly technical and extremely mathematical articles published about optical modulation formats, showing complex formulas, spectral diagrams and almost unreadable eye diagrams, which can be considered normal for every emerging technology. The main purpose of this article is to demystify optical modulation in a way that the rest of us can visualize and understand them. Nevertheless, some of these modulations are so complex that they can’t be properly represented in a simple time domain graph, so polar (constellation) or spherical coordinates are often used to represent the different states of the signal. Within this document some of these polar diagrams have been enhanced with the state diagram (blue) to indicate the possible transitions and logic. Introduction Back in the early ‘90s, copper lines moved from digital baseband line coding (e.g. 2B1Q, 4B3T, AMI, and HDB3, among others) to complex modulation schemes to increase speed, reach, and reliability. We were all skeptical that a technology like DSL would have been able to transmit 256 simultaneous QAM16 signals and achieve 8 Mbit/s. Today copper is already reaching the 155 Mbit/s mark. This is certainly a full circle. We moved from analog to digital transmission to increase data rates and reliability, and then we resorted to analog signals (through modulation) to carry digital information farther, faster and more reliably. Back then, 155 Mbit/s were only thought of for fiber optics transmission. It is also interesting to note that only a few years ago we seemed to be under the impression that ‘fiber optics offered an almost infinite amount of bandwidth’ or more than we would ever need.
    [Show full text]
  • P802.3Ah Draft 2.0 Comments
    P802.3ah Draft 2.0 Comments Cl 00 SC P L # 952 Cl 00 SC P L # 1248 Thompson, Geoff Nortel Lee Sendelbach IBM Comment Type TR Comment Status R Comment Type E Comment Status A What is being proposed in many places throughout this draft is not a peer network. To Fix all the references with *ref*. Like 60.9.4, 60.8.13.2.1, 60.8.13.1 60.8.11 60.1 I don't introduce such a foreign concept into a document where the implicit and explicit notion of understand what is going on with the *refs. Also fix #CrossRef# in 64.1 peer relationships is so thoroughly infused throughout the existing document is likely to SuggestedRemedy cause (a) significant confusion and (b) significant errors. Fix it. SuggestedRemedy Move non-peer proposals to a new and separate document that can thoroughly, explicitly Proposed Response Response Status C and unambigiously embrace the concept of Ethernet Services over asymetrical ACCEPT IN PRINCIPLE. infrastructure. These references are intended for the use of the editors to search for cross references. All Proposed Response Response Status U these will be romeved at time of publication as indicated in the editor's note boxes REJECT. Cl 00 SC P L # 951 The suggested remedy is ambiguous. What are "the non-peer proposals"? What is the Thompson, Geoff Nortel "new and separate document"? Comment Type TR Comment Status A reassigned The draft in its current form satisfies the PAR and 5 Criteria for the project, which call for an I have a problem with the use of the term "loopback" for the diagnostic return path being amendment to IEEE Std 802.3, formatted as a set of clauses.
    [Show full text]