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onsemi and and other names, marks, and brands are registered and/or common law trademarks of Semiconductor Components Industries, LLC dba “onsemi” or its affiliates and/or subsidiaries in the United States and/or other countries. onsemi owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. A listing of onsemi product/patent coverage may be accessed at www.onsemi.com/site/pdf/Patent-Marking.pdf. onsemi reserves the right to make changes at any time to any products or information herein, without notice. The information herein is provided “as-is” and onsemi makes no warranty, representation or guarantee regarding the accuracy of the information, product features, availability, functionality, or suitability of its products for any particular purpose, nor does onsemi assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. Buyer is responsible for its products and applications using onsemi products, including compliance with all laws, regulations and safety requirements or standards, regardless of any support or applications information provided by onsemi. “Typical” parameters which may be provided in onsemi data sheets and/ or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. onsemi does not convey any license under any of its intellectual property rights nor the rights of others. onsemi products are not designed, intended, or authorized for use as a critical component in life support systems or any FDA Class 3 medical devices or medical devices with a same or similar classification in a foreign jurisdiction or any devices intended for implantation in the human body. Should Buyer purchase or use onsemi products for any such unintended or unauthorized application, Buyer shall indemnify and holdonsemi and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that onsemi was negligent regarding the design or manufacture of the part. onsemi is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner. Other names and brands may be claimed as the property of others. MC33035, NCV33035

Brushless DC Motor Controller

The MC33035 is a high performance second generation monolithic brushless DC motor controller containing all of the active functions required to implement a full featured open loop, three or four phase motor control system. This device consists of a position decoder http://onsemi.com for proper commutation sequencing, temperature compensated reference capable of supplying sensor power, frequency programmable sawtooth oscillator, three open collector top drivers, and three high current totem pole bottom drivers ideally suited for PDIP−24 P SUFFIX driving power MOSFETs. CASE 724 24 Also included are protective features consisting of undervoltage 1 lockout, cycle−by−cycle current limiting with a selectable time delayed latched shutdown mode, internal thermal shutdown, and a unique fault output that can be interfaced into microprocessor SOIC−24 WB DW SUFFIX controlled systems. CASE 751E 24 Typical motor control functions include open loop speed, forward or 1 reverse direction, run enable, and dynamic braking. The MC33035 is designed to operate with electrical sensor phasings of 60°/300° or 120°/240°, and can also efficiently control DC motors. PIN CONNECTIONS Features

• 10 to 30 V Operation Top Drive BT 1 24 CT Output • Undervoltage Lockout AT 2 23 Brake • 6.25 V Reference Capable of Supplying Sensor Power Fwd/Rev 3 22 60°/120° Select • Fully Accessible Error Amplifier for Closed Loop Servo Applications SA 4 21 AB Bottom • Sensor High Current Drivers Can Control External 3−Phase MOSFET S 5 20 B Drive Inputs B B Bridge Outputs S • Cycle−By−Cycle Current Limiting C 6 19 CB

• Pinned−Out Current Sense Reference Output Enable 7 18 VC • Internal Thermal Shutdown Reference Output 8 17 VCC • Selectable 60°/300° or 120°/240° Sensor Phasings Current Sense 9 16 Gnd • Can Efficiently Control Brush DC Motors with External MOSFET Noninverting Input Current Sense 10 15 H−Bridge Oscillator Inverting Input • Error Amp NCV Prefix for Automotive and Other Applications Requiring 11 14 Noninverting Input Fault Output Unique Site and Control Change Requirements; AEC−Q100 Error Amp Error Amp Out/ 12 13 Qualified and PPAP Capable Inverting Input PWM Input • Pb−Free Packages are Available (Top View)

ORDERING INFORMATION See detailed ordering and shipping information in the package dimensions section on page 28 of this data sheet.

DEVICE MARKING INFORMATION See general marking information in the device marking section on page 28 of this data sheet.

© Semiconductor Components Industries, LLC, 2014 1 Publication Order Number: May, 2014 − Rev. 9 MC33035/D MC33035, NCV33035

Representative Schematic Diagram

VM Fault 14 N 4 S S N 5 2 Rotor 6 Position Decoder 1 Fwd/Rev 3 60°/120° 22 24 Motor Enable 7 Undervoltage Vin Output 17 Lockout Buffers 18 Reference Regulator 8 21 Speed Set 11 Error Amp Thermal Faster 12 Shutdown 20 PWM RT 13 R Q S 19

Oscillator S 10 CT Q R 9

15

16 23 Current Sense Brake Reference

This device contains 285 active transistors.

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MAXIMUM RATINGS Rating Symbol Value Unit

Power Supply VCC 40 V

Digital Inputs (Pins 3, 4, 5, 6, 22, 23) − Vref V

Oscillator Input Current (Source or Sink) IOSC 30 mA

Error Amp Input Voltage Range (Pins 11, 12, Note 1) VIR −0.3 to Vref V

Error Amp Output Current (Source or Sink, Note 2) IOut 10 mA

Current Sense Input Voltage Range (Pins 9, 15) VSense −0.3 to 5.0 V

Fault Output Voltage VCE(Fault) 20 V

Fault Output Sink Current ISink(Fault) 20 mA

Top Drive Voltage (Pins 1, 2, 24) VCE(top) 40 V

Top Drive Sink Current (Pins 1, 2, 24) ISink(top) 50 mA

Bottom Drive Supply Voltage (Pin 18) VC 30 V

Bottom Drive Output Current (Source or Sink, Pins 19, 20, 21) IDRV 100 mA Electrostatic Discharge Sensitivity (ESD) Human Body Model (HBM) Class 2, JESD22 A114−C − 2000 V Machine Model (MM) Class A, JESD22 A115−A − 200 V Charged Device Model (CDM), JESD22 C101−C − 2000 V Power Dissipation and Thermal Characteristics P Suffix, Dual In Line, Case 724 Maximum Power Dissipation @ TA = 85°C PD 867 mW Thermal Resistance, Junction−to−Air RθJA 75 °C/W DW Suffix, Surface Mount, Case 751E Maximum Power Dissipation @ TA = 85°C PD 650 mW Thermal Resistance, Junction−to−Air RθJA 100 °C/W

Operating Junction Temperature TJ 150 °C

Operating Ambient Temperature Range (Note 3) MC33035 TA −40 to +85 °C NCV33035 −40 to +125

Storage Temperature Range Tstg −65 to +150 °C Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability.

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ELECTRICAL CHARACTERISTICS (VCC = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.) Characteristic Symbol Min Typ Max Unit REFERENCE SECTION

Reference Output Voltage (Iref = 1.0 mA) Vref V TA = 25°C 5.9 6.24 6.5 (Note 4) 5.82 − 6.57

Line Regulation (VCC = 10 to 30 V, Iref = 1.0 mA) Regline − 1.5 30 mV

Load Regulation (Iref = 1.0 to 20 mA) Regload − 16 30 mV

Output Short Circuit Current (Note 5) ISC 40 75 − mA

Reference Under Voltage Lockout Threshold Vth 4.0 4.5 5.0 V ERROR AMPLIFIER

Input Offset Voltage (Note 4) VIO − 0.4 10 mV

Input Offset Current (Note 4) IIO − 8.0 500 nA

Input Bias Current (Note 4) IIB − −46 −1000 nA

Input Common Mode Voltage Range VICR (0 V to Vref) V

Open Loop Voltage Gain (VO = 3.0 V, RL = 15 k) AVOL 70 80 − dB Input Common Mode Rejection Ratio CMRR 55 86 − dB

Power Supply Rejection Ratio (VCC = VC = 10 to 30 V) PSRR 65 105 − dB Output Voltage Swing V High State (RL = 15 k to Gnd) VOH 4.6 5.3 − Low State (RL = 15 k to Vref) VOL − 0.5 1.0 OSCILLATOR SECTION

Oscillator Frequency fOSC 22 25 28 kHz

Frequency Change with Voltage (VCC = 10 to 30 V) ΔfOSC/ΔV − 0.01 5.0 %

Sawtooth Peak Voltage VOSC(P) − 4.1 4.5 V

Sawtooth Valley Voltage VOSC(V) 1.2 1.5 − V LOGIC INPUTS Input Threshold Voltage (Pins 3, 4, 5, 6, 7, 22, 23) V High State VIH 3.0 2.2 − Low State VIL − 1.7 0.8 Sensor Inputs (Pins 4, 5, 6) μA High State Input Current (VIH = 5.0 V) IIH −150 −70 −20 Low State Input Current (VIL = 0 V) IIL −600 −337 −150 Forward/Reverse, 60°/120° Select (Pins 3, 22, 23) μA High State Input Current (VIH = 5.0 V) IIH −75 −36 −10 Low State Input Current (VIL = 0 V) IIL −300 −175 −75 Output Enable μA High State Input Current (VIH = 5.0 V) IIH −60 −29 −10 Low State Input Current (VIL = 0 V) IIL −60 −29 −10 CURRENT−LIMIT COMPARATOR

Threshold Voltage Vth 85 101 115 mV

Input Common Mode Voltage Range VICR − 3.0 − V

Input Bias Current IIB − −0.9 −5.0 μA OUTPUTS AND POWER SECTIONS

Top Drive Output Sink Saturation (Isink = 25 mA) VCE(sat) − 0.5 1.5 V

Top Drive Output Off−State Leakage (VCE = 30 V) IDRV(leak) − 0.06 100 μA

Top Drive Output Switching Time (CL = 47 pF, RL = 1.0 k) ns Rise Time tr − 107 300 Fall Time tf − 26 300 Bottom Drive Output Voltage V High State (VCC = 20 V, VC = 30 V, Isource = 50 mA) VOH (VCC −2.0) (VCC −1.1) − Low State (VCC = 20 V, VC = 30 V, Isink = 50 mA) VOL − 1.5 2.0

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ELECTRICAL CHARACTERISTICS (VCC = VC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.) Characteristic Symbol Min Typ Max Unit

OUTPUTS AND POWER SECTIONS

Bottom Drive Output Switching Time (CL = 1000 pF) ns Rise Time tr − 38 200 Fall Time tf − 30 200

Fault Output Sink Saturation (Isink = 16 mA) VCE(sat) − 225 500 mV

Fault Output Off−State Leakage (VCE = 20 V) IFLT(leak) − 1.0 100 μA Under Voltage Lockout V

Drive Output Enabled (VCC or VC Increasing) Vth(on) 8.2 8.9 10 Hysteresis VH 0.1 0.2 0.3 Power Supply Current mA Pin 17 (VCC = VC = 20 V) ICC − 12 16 Pin 17 (VCC = 20 V, VC = 30 V) − 14 20 Pin 18 (VCC = VC = 20 V) IC − 3.5 6.0 Pin 18 (VCC = 20 V, VC = 30 V) − 5.0 10 1. The input common mode voltage or input signal voltage should not be allowed to go negative by more than 0.3 V. 2. The compliance voltage must not exceed the range of −0.3 to Vref. 3. NCV33035: Tlow = −40°C, Thigh = 125°C. Guaranteed by design. NCV prefix is for automotive and other applications requiring site and change control. 4. MC33035: TA = −40°C to +85°C; NCV33035: TA = −40°C to +125°C. 5. Maximum package power dissipation limits must be observed.

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100 4.0 VCC = 20 V VCC = 20 V ° TA = 25 C VC = 20 V R = 4.7 k 2.0 T CT = 10 nF

CT = 1.0 nF 10 0

-2.0 OSCILLATOR FREQUENCY (kHz) FREQUENCY OSCILLATOR , OSCILLATOR FREQUENCY CHANGE (%) FREQUENCY OSCILLATOR OSC , f CT = 100 nF C = 10 nF 1.0 T -4.0 OSC

1.0 10 100 f -55 -25 0 25 50 75 100 125 Δ RT, TIMING RESISTOR (kΩ) TA, AMBIENT TEMPERATURE (°C) Figure 1. Oscillator Frequency versus Figure 2. Oscillator Frequency Change Timing Resistor versus Temperature

56 40 0 V 48 60 ref VCC = 20 V VC = 20 V 40 80 - 0.8 Source Saturation T = 25°C Phase (Load to Ground) A 32 100 24 120 -1.6 16 Gain 140 V = 20 V 8.0 CC 160 1.6 VC = 20 V 0 VO = 3.0 V 180

RL = 15 k EXCESS PHASE (DEGREES) Sink Saturation 200 , , OPEN LOOP VOLTAGE GAIN (dB) VOLTAGE , OPEN LOOP 0.8

-8.0 φ CL = 100 pF Gnd (Load to Vref) -16 ° 220 (V) VOLTAGE SATURATION , OUTPUT VOL TA = 25 C sat A -24 240 V 0 1.0 k 10 k 100 k 1.0 M 10 M 0 1.0 2.0 3.0 4.0 5.0

f, FREQUENCY (Hz) IO, OUTPUT LOAD CURRENT (mA) Figure 3. Error Amp Open Loop Gain and Figure 4. Error Amp Output Saturation Phase versus Frequency Voltage versus Load Current

AV = +1.0 AV = +1.0 No Load No Load 3.05 ° 4.5 TA = 25 C TA = 25°C

3.0 3.0 , OUTPUT VOLTAGE (V) VOLTAGE , OUTPUT , OUTPUT VOLTAGE (V) VOLTAGE , OUTPUT O O V 2.95 V 1.5

1.0 μs/DIV 5.0 μs/DIV Figure 5. Error Amp Small−Signal Figure 6. Error Amp Large−Signal Transient Response Transient Response

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0 7.0

6.0 -4.0 5.0 -8.0 4.0 - 12 3.0 - 16 2.0

VCC = 20 V -20 1.0 No Load VC = 20 V (V) VOLTAGE , REFERENCE OUTPUT ° TA = 25°C TA = 25 C ref -24 V 0 0 10 20 30 40 50 60 0 10 20 30 40

, REFERENCE OUTPUT VOLTAGE CHANGE (mV) VOLTAGE , REFERENCE OUTPUT Iref, REFERENCE OUTPUT SOURCE CURRENT (mA) VCC, SUPPLY VOLTAGE (V) ref V

Δ Figure 7. Reference Output Voltage Change Figure 8. Reference Output Voltage versus Output Source Current versus Supply Voltage

100 V = 20 V 40 CC VC = 20 V 80 RT = 4.7 k C = 10 nF 20 T TA = 25°C 60 0 40 -20 VCC = 20 V OUTPUT DUTY CYCLE (%) DUTY OUTPUT 20 VC = 20 V -40 No Load 0 , NORMALIZED REFERENCE VOLTAGE CHANGE (mV) , NORMALIZED REFERENCE VOLTAGE -55-25 0 25 50 75 100 125 0 1.0 2.0 3.0 4.0 5.0 ref V T , AMBIENT TEMPERATURE (°C) PWM INPUT VOLTAGE (V) Δ A Figure 9. Reference Output Voltage Figure 10. Output Duty Cycle versus versus Temperature PWM Input Voltage

250 0.25 VCC = 20 V VCC = 20 V VC = 20 V VC = 20 V 1 0.2 200 RL = TA = 25°C CL = 1.0 nF TA = 25°C 150 0.15

100 0.1

50 0.05 , OUTPUT SATURATION VOLTAGE (V) VOLTAGE SATURATION , OUTPUT , BOTTOM DRIVE RESPONSE TIME (ns) DRIVE RESPONSE , BOTTOM sat HL V t 0 0 1.0 2.0 3.0 4.0 5.06.0 7.0 8.09.0 10 0164.0 8.0 12

CURRENT SENSE INPUT VOLTAGE (NORMALIZED TO Vth) ISink, SINK CURRENT (mA) Figure 11. Bottom Drive Response Time versus Figure 12. Fault Output Saturation Current Sense Input Voltage versus Sink Current

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1.2 VCC = 20 V V = 20 V C 100 TA = 25°C 0.8

V = 20 V 0.4 CC VC = 20 V RL = 1.0 k 0 CL = 15 pF , OUTPUT SATURATION VOLTAGE (V) VOLTAGE SATURATION , OUTPUT TA = 25°C sat V 0 0 1020 30 40 100 ns/DIV ISink, SINK CURRENT (mA) Figure 13. Top Drive Output Saturation Figure 14. Top Drive Output Waveform Voltage versus Sink Current

V = 20 V VCC = 20 V CC V = 20 V VC = 20 V C C = 15 pF 100 CL = 1.0 nF 100 L T = 25°C TA = 25°C A OUTPUT VOLTAGE (%) VOLTAGE OUTPUT OUTPUT VOLTAGE (%) VOLTAGE OUTPUT (%) VOLTAGE OUTPUT 0 0

50 ns/DIV 50 ns/DIV Figure 15. Bottom Drive Output Waveform Figure 16. Bottom Drive Output Waveform

0 16 VC 14 -1.0 ICC Source Saturation VCC = 20 V 12 (Load to Ground) R = 4.7 k -2.0 VC = 20 V T 10 C = 10 nF TA = 25°C T Pins 3-6, 9, 15, 23 = Gnd 8.0 Pins 7, 22 = Open TA = 25°C 6.0 2.0 4.0 Sink Saturation , POWER SUPPLY CURRENT (mA) CURRENT , POWER SUPPLY IC 1.0 (Load to V ) Gnd CC , OUTPUT SATURATION VOLTAGE (V) VOLTAGE SATURATION , OUTPUT C 2.0 , I sat C V 0 I 0 0 20 40 60 80 0 5.0 10 15 20 25 30

IO, OUTPUT LOAD CURRENT (mA) VCC, SUPPLY VOLTAGE (V) Figure 17. Bottom Drive Output Saturation Figure 18. Power and Bottom Drive Supply Voltage versus Load Current Current versus Supply Voltage

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PIN FUNCTION DESCRIPTION Pin Symbol Description

1, 2, 24 BT, AT, CT These three open collector Top Drive outputs are designed to drive the external upper power switch transistors. 3 Fwd/Rev The Forward/Reverse Input is used to change the direction of motor rotation.

4, 5, 6 SA, SB, SC These three Sensor Inputs control the commutation sequence. 7 Output Enable A logic high at this input causes the motor to run, while a low causes it to coast.

8 Reference Output This output provides charging current for the oscillator timing capacitor CT and a reference for the error amplifier. It may also serve to furnish sensor power. 9 Current Sense Noninverting Input A 100 mV signal, with respect to Pin 15, at this input terminates output switch conduction during a given oscillator cycle. This pin normally connects to the top side of the current sense resistor. 10 Oscillator The Oscillator frequency is programmed by the values selected for the timing components, RT and CT. 11 Error Amp Noninverting Input This input is normally connected to the speed set potentiometer. 12 Error Amp Inverting Input This input is normally connected to the Error Amp Output in open loop applications. 13 Error Amp Out/PWM Input This pin is available for compensation in closed loop applications. 14 Fault Output This open collector output is active low during one or more of the following conditions: Invalid Sensor Input code, Enable Input at logic 0, Current Sense Input greater than 100 mV (Pin 9 with respect to Pin 15), Undervoltage Lockout activation, and Thermal Shutdown. 15 Current Sense Inverting Input Reference pin for internal 100 mV threshold. This pin is normally connected to the bottom side of the current sense resistor. 16 Gnd This pin supplies a ground for the control circuit and should be referenced back to the power source ground.

17 VCC This pin is the positive supply of the control IC. The controller is functional over a minimum VCC range of 10 to 30 V.

18 VC The high state (VOH) of the Bottom Drive Outputs is set by the voltage applied to this pin. The controller is operational over a minimum VC range of 10 to 30 V.

19, 20, 21 CB, BB, AB These three totem pole Bottom Drive Outputs are designed for direct drive of the external bottom power switch transistors. 22 60°/120° Select The electrical state of this pin configures the control circuit operation for either 60° (high state) or 120° (low state) sensor electrical phasing inputs. 23 Brake A logic low state at this input allows the motor to run, while a high state does not allow motor operation and if operating causes rapid deceleration.

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INTRODUCTION the winding. When the input changes state, from high The MC33035 is one of a series of high performance to low with a given sensor input code (for example 100), the monolithic DC brushless motor controllers produced by enabled top and bottom drive outputs with the same alpha Motorola. It contains all of the functions required to designation are exchanged (AT to AB, BT to BB, CT to CB). implement a full−featured, open loop, three or four phase In effect, the commutation sequence is reversed and the motor control system. In addition, the controller can be made motor changes directional rotation. to operate DC brush motors. Constructed with Bipolar Motor on/off control is accomplished by the Output Analog technology, it offers a high degree of performance and Enable (Pin 7). When left disconnected, an internal 25 μA ruggedness in hostile industrial environments. The MC33035 current source enables sequencing of the top and bottom contains a rotor position decoder for proper commutation drive outputs. When grounded, the top drive outputs turn off sequencing, a temperature compensated reference capable of and the bottom drives are forced low, causing the motor to supplying a sensor power, a frequency programmable coast and the Fault output to activate. sawtooth oscillator, a fully accessible error amplifier, a pulse Dynamic motor braking allows an additional margin of width modulator comparator, three open collector top drive safety to be designed into the final product. Braking is outputs, and three high current totem pole bottom driver accomplished by placing the Brake Input (Pin 23) in a high outputs ideally suited for driving power MOSFETs. state. This causes the top drive outputs to turn off and the Included in the MC33035 are protective features bottom drives to turn on, shorting the motor−generated back consisting of undervoltage lockout, cycle−by−cycle current EMF. The brake input has unconditional priority over all limiting with a selectable time delayed latched shutdown other inputs. The internal 40 kΩ pull−up resistor simplifies mode, internal thermal shutdown, and a unique fault output interfacing with the system safety−switch by insuring brake that can easily be interfaced to a microprocessor controller. activation if opened or disconnected. The commutation Typical motor control functions include open loop speed logic truth table is shown in Figure 20. A four input NOR control, forward or reverse rotation, run enable, and gate is used to monitor the brake input and the inputs to the dynamic braking. In addition, the MC33035 has a 60°/120° three top drive output transistors. Its purpose is to disable select pin which configures the rotor position decoder for braking until the top drive outputs attain a high state. This either 60° or 120° sensor electrical phasing inputs. helps to prevent simultaneous conduction of the the top and bottom power switches. In half wave FUNCTIONAL DESCRIPTION applications, the top drive outputs are not required and are A representative internal block diagram is shown in normally left disconnected. Under these conditions braking Figure 19 with various applications shown in Figures 36, 38, will still be accomplished since the NOR gate senses the 39, 43, 45, and 46. A discussion of the features and function base voltage to the top drive output transistors. of each of the internal blocks given below is referenced to Figures 19 and 36. Error Amplifier A high performance, fully compensated error amplifier Rotor Position Decoder with access to both inputs and output (Pins 11, 12, 13) is An internal rotor position decoder monitors the three provided to facilitate the implementation of closed loop sensor inputs (Pins 4, 5, 6) to provide the proper sequencing motor speed control. The amplifier features a typical DC of the top and bottom drive outputs. The sensor inputs are voltage gain of 80 dB, 0.6 MHz gain bandwidth, and a wide designed to interface directly with open collector type Hall input common mode voltage range that extends from ground Effect switches or opto slotted couplers. Internal pull−up to Vref. In most open loop speed control applications, the resistors are included to minimize the required number of amplifier is configured as a unity gain voltage follower with external components. The inputs are TTL compatible, with the noninverting input connected to the speed set voltage their thresholds typically at 2.2 V. The MC33035 series is source. Additional configurations are shown in Figures 31 designed to control three phase motors and operate with four through 35. of the most common conventions of sensor phasing. A 60°/120° Select (Pin 22) is conveniently provided and Oscillator affords the MC33035 to configure itself to control motors The frequency of the internal ramp oscillator is having either 60°, 120°, 240° or 300° electrical sensor programmed by the values selected for timing components phasing. With three sensor inputs there are eight possible RT and CT. Capacitor CT is charged from the Reference input code combinations, six of which are valid rotor Output (Pin 8) through resistor RT and discharged by an positions. The remaining two codes are invalid and are internal discharge transistor. The ramp peak and valley usually caused by an open or shorted sensor line. With six are typically 4.1 V and 1.5 V respectively. To valid input codes, the decoder can resolve the motor rotor provide a good compromise between audible noise and position to within a window of 60 electrical degrees. output switching efficiency, an oscillator frequency in the The Forward/Reverse input (Pin 3) is used to change the range of 20 to 30 kHz is recommended. Refer to Figure 1 for direction of motor rotation by reversing the voltage across component selection.

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VM 20 k 14 4 Fault Output SA 20 k 5 2 Sensor SB Inputs 20 k AT 6 Rotor SC 1 Top Position Drive 3 40 k Decoder B Forward/Reverse T Outputs 22 40 k 24 60°/120° Select C 7 25 μA T Output Enable 17 Undervoltage Vin V Lockout CC18 VC Reference Regulator 9.1 V Reference Output 8 21 AB

Noninv. Input 4.5 V 11 Error Amp Bottom Thermal 20 BB Drive Faster 12 Shutdown PWM Outputs RT 13 Latch Error Amp Out R 19 PWM Input Q CB S Latch 10 Oscillator S Q 40 k CT 9 R Current Sense Input Sink Only Current Sense 100 mV 15 = Positive True Reference Input Logic With Hysteresis 16 Gnd 23 Brake Input

Figure 19. Representative Block Diagram

Inputs (Note 2) Outputs (Note 3) Sensor Electrical Phasing (Note 4) Top Drives Bottom Drives 60° 120° Current SA SB SC SA SB SC F/R Enable Brake Sense AT BT CT AB BB CB Fault 1 0 0 1 0 0 1 1 0 0 0 1 1 0 0 1 1 (Note 5) 1 1 0 1 1 0 1 1 0 0 1 0 1 0 0 1 1 F/R = 1 1 1 1 0 1 0 1 1 0 0 1 0 1 1 0 0 1 0 1 1 0 1 1 1 1 0 0 1 1 0 1 0 0 1 0 0 1 0 0 1 1 1 0 0 1 1 0 0 1 0 1 0 0 0 1 0 1 1 1 0 0 0 1 1 0 1 0 1 1 0 0 1 0 0 0 1 0 0 1 1 0 1 0 0 1 (Note 5) 1 1 0 1 1 0 0 1 0 0 1 1 0 0 1 0 1 F/R = 0 1 1 1 0 1 0 0 1 0 0 0 1 1 0 1 0 1 0 1 1 0 1 1 0 1 0 0 0 1 1 0 0 1 1 0 0 1 0 0 1 0 1 0 0 1 0 1 0 0 1 1 0 0 0 1 0 1 0 1 0 0 1 0 1 1 0 0 1 1 0 1 1 1 1 X X 0 X 1 1 1 0 0 0 0 (Note 6) 0 1 0 0 0 0 X X 0 X 1 1 1 0 0 0 0 Brake = 0 1 0 1 1 1 1 X X 1 X 1 1 1 1 1 1 0 (Note 7) 0 1 0 0 0 0 X X 1 X 1 1 1 1 1 1 0 Brake = 1 V V V V V V X 1 1 X 1 1 1 1 1 1 1 (Note 8) V V V V V V X 0 1 X 1 1 1 1 1 1 0 (Note 9) V V V V V V X 0 0 X 1 1 1 0 0 0 0 (Note 10)

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V V V V V V X 1 0 1 1 1 1 0 0 0 0 (Note 11) NOTES: 1. V = Any one of six valid sensor or drive combinations X = Don’t care. 2. The digital inputs (Pins 3, 4, 5, 6, 7, 22, 23) are all TTL compatible. The current sense input (Pin 9) has a 100 mV threshold with respect to Pin 15. A logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV. 3. The fault and top drive outputs are open collector design and active in the low (0) state. 4. With 60°/120° select (Pin 22) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 22 in low (0) state, configuration is for 120° sensor electrical phasing inputs. 5. Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs. 6. Invalid sensor inputs with brake = 0; All top and bottom drives off, Fault low. 7. Invalid sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault low. 8. Valid 60° or 120° sensor inputs with brake = 1; All top drives off, all bottom drives on, Fault high. 9. Valid sensor inputs with brake = 1 and enable = 0; All top drives off, all bottom drives on, Fault low. 10. Valid sensor inputs with brake = 0 and enable = 0; All top and bottom drives off, Fault low. 11. All bottom drives off, Fault low. Figure 20. Three Phase, Six Step Commutation Truth Table (Note 1)

Pulse Width Modulator sensing an over current condition, immediately turning off The use of pulse width modulation provides an energy the switch and holding it off for the remaining duration of efficient method of controlling the motor speed by varying oscillator ramp−up period. The stator current is converted to the average voltage applied to each stator winding during the a voltage by inserting a ground−referenced sense resistor RS commutation sequence. As CT discharges, the oscillator sets (Figure 36) in series with the three bottom switch transistors both latches, allowing conduction of the top and bottom (Q4, Q5, Q6). The voltage developed across the sense drive outputs. The PWM comparator resets the upper latch, resistor is monitored by the Current Sense Input (Pins 9 and terminating the bottom drive output conduction when the 15), and compared to the internal 100 mV reference. The positive−going ramp of CT becomes greater than the error current sense comparator inputs have an input common amplifier output. The pulse width modulator timing diagram mode range of approximately 3.0 V. If the 100 mV current is shown in Figure 21. Pulse width modulation for speed sense threshold is exceeded, the comparator resets the lower control appears only at the bottom drive outputs. sense latch and terminates output switch conduction. The value for the current sense resistor is: Current Limit R + 0.1 Continuous operation of a motor that is severely S I over−loaded results in overheating and eventual failure. stator(max) This destructive condition can best be prevented with the use The Fault output activates during an over current condition. of cycle−by−cycle current limiting. That is, each on−cycle The dual−latch PWM configuration ensures that only one is treated as a separate event. Cycle−by−cycle current single output conduction pulse occurs during any given limiting is accomplished by monitoring the stator current oscillator cycle, whether terminated by the output of the build−up each time an output switch conducts, and upon error amp or the current limit comparator.

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Undervoltage Lockout Capacitor C T A triple Undervoltage Lockout has been incorporated to Error Amp Out/PWM prevent damage to the IC and the external power switch Input transistors. Under low power supply conditions, it Current guarantees that the IC and sensors are fully functional, and Sense Input that there is sufficient bottom drive output voltage. The positive power supplies to the IC (VCC) and the bottom Latch “Set" Inputs drives (VC) are each monitored by separate comparators that have their thresholds at 9.1 V. This level ensures sufficient gate drive necessary to attain low R when driving Top Drive DS(on) Outputs standard power MOSFET devices. When directly powering the Hall sensors from the reference, improper sensor Bottom Drive operation can result if the reference output voltage falls Outputs below 4.5 V. A third comparator is used to detect this condition. If one or more of the comparators detects an Fault Output undervoltage condition, the Fault Output is activated, the top drives are turned off and the bottom drive outputs are held in a low state. Each of the comparators contain hysteresis to Figure 21. Pulse Width Modulator Timing Diagram prevent oscillations when crossing their respective Reference thresholds. The on−chip 6.25 V regulator (Pin 8) provides charging current for the oscillator timing capacitor, a reference for the Fault Output error amplifier, and can supply 20 mA of current suitable for The open collector Fault Output (Pin 14) was designed to directly powering sensors in low voltage applications. In provide diagnostic information in the event of a system higher voltage applications, it may become necessary to malfunction. It has a sink current capability of 16 mA and transfer the power dissipated by the regulator off the IC. This can directly drive a light emitting diode for visual indication. is easily accomplished with the addition of an external pass Additionally, it is easily interfaced with TTL/CMOS logic transistor as shown in Figure 22. A 6.25 V reference level for use in a microprocessor controlled system. The Fault was chosen to allow implementation of the simpler NPN Output is active low when one or more of the following circuit, where Vref − VBE exceeds the minimum voltage conditions occur: required by Hall Effect sensors over temperature. With 1) Invalid Sensor Input code proper transistor selection and adequate heatsinking, up to 2) Output Enable at logic [0] one amp of load current can be obtained. 3) Current Sense Input greater than 100 mV UVLO 17 4) Undervoltage Lockout, activation of one or more of Vin the comparators 18 5) Thermal Shutdown, maximum junction temperature REF being exceeded This unique output can also be used to distinguish between MPS 8 motor start−up or sustained operation in an overloaded U01A condition. With the addition of an RC network between the To Fault Output and the enable input, it is possible to create a Control Sensor time−delayed latched shutdown for overcurrent. The added Power Circuitry ≈5.6 V 6.25 V circuitry shown in Figure 23 makes easy starting of motor UVLO 39 17 systems which have high inertial loads by providing Vin additional starting torque, while still preserving overcurrent 18 protection. This task is accomplished by setting the current limit to a higher than nominal value for a predetermined time. REF MPS During an excessively long overcurrent condition, capacitor U51A 0.1 8 CDLY will charge, causing the enable input to cross its threshold to a low state. A latch is then formed by the positive To Control Circuitry feedback loop from the Fault Output to the Output Enable. and Sensor Power Once set, by the Current Sense Input, it can only be reset by 6.25 V shorting CDLY or cycling the power supplies. The NPN circuit is recommended for powering Hall or opto sensors, where the output voltage temperature coefficient is not critical. The PNP circuit is slightly more complex, but is also more accurate over temperature. Neither circuit has current limiting. Figure 22. Reference Output Buffers

http://onsemi.com 13 MC33035, NCV33035

Drive Outputs of VCC. A zener clamp should be connected to this input The three top drive outputs (Pins 1, 2, 24) are open when driving power MOSFETs in systems where VCC is collector NPN transistors capable of sinking 50 mA with a greater than 20 V so as to prevent rupture of the MOSFET minimum breakdown of 30 V. Interfacing into higher gates. voltage applications is easily accomplished with the circuits The control circuitry ground (Pin 16) and current sense shown in Figures 24 and 25. inverting input (Pin 15) must return on separate paths to the The three totem pole bottom drive outputs (Pins 19, 20, central input source ground. 21) are particularly suited for direct drive of N−Channel Thermal Shutdown MOSFETs or NPN bipolar transistors (Figures 26, 27, 28 Internal thermal shutdown circuitry is provided to protect and 29). Each output is capable of sourcing and sinking up the IC in the event the maximum junction temperature is to 100 mA. Power for the bottom drives is supplied from V C exceeded. When activated, typically at 170°C, the IC acts as (Pin 18). This separate supply input allows the designer though the Output Enable was grounded. added flexibility in tailoring the drive voltage, independent

14 14 4 VM 2 5 2 VCC Q2 Rotor Q Q 6 Position 1 1 3 POS 1 Decoder DEC RDLY 3 24 22 24 Load

17 UVLO VM 18

REF 21 Reset 21 8

CDLY 20 Q4 25 μA 20 7

19

V –(I enable R ) t [ R C Inǒ ref IL DLY Ǔ DLY DLY DLY V enable – (I enable R ) th IL DLY

6.25 – (20 x 10–6 R ) [ ǒ DLY Ǔ Transistor Q1 is a common base stage used to level shift from VCC to the R C In high motor voltage, V . The collector diode is required if V is present DLY DLY 1.4 – (20 x 10–6 R ) M CC DLY while VM is low.

Figure 23. Timed Delayed Latched Figure 24. High Voltage Interface with Over Current Shutdown NPN Power Transistors

http://onsemi.com 14 MC33035, NCV33035

14 VBoost VM = 170 V VCC = 12 V

2 1.0 k 5 1 Rotor 6 Position 1 2 1.0 M 4 Decoder 21 4.7 k

24 1N4744 20 MOC8204 Optocoupler Load 19

21 40 k 9 R

20 C RS Q4 100 mV 15

23 Brake Input 19 The addition of the RC filter will eliminate current−limit instability caused by the leading edge spike on the current waveform. Resistor RS should be a low in- ductance type.

Figure 25. High Voltage Interface with Figure 26. Current Waveform Spike Suppression N−Channel Power MOSFETs

C 21 Rg 21 D C 20 Rg 20 D C 19 Rg 19 D IB

40 k 40 k + 9 9 0 t - 100 mV 15 100 mV 15 Base Charge D = 1N5819 23 Brake Input 23 Brake Input Removal

Series gate resistor Rg will dampen any high frequency oscillations caused The totem−pole output can furnish negative base current for enhanced tran- by the MOSFET input capacitance and any series wiring induction in the sistor turn−off, with the addition of capacitor C. gate−source circuit. Diode D is required if the negative current into the Bot- tom Drive Outputs exceeds 50 mA.

Figure 27. MOSFET Drive Precautions Figure 28. Bipolar Transistor Drive

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D SENSEFET 21 G S M K

20

VM + 12 19 V = 12 V CC VM + 8.0 Power Ground: 9 To Input Source Return 8 4 R R @ I @ R 7 Boost (V) Voltage VM + 4.0 15 S S pk DS(on) 6 0 20 40 60 V [ 100 mV Pin 9 r ) R R Boost Current (mA) DM(on) S 5 Q 3 1.0/200 V * If: SENSEFET = MPT10N10M S VBoost 16 Gnd R = 200 Ω, 1/4 W S 2 22 ≈ 1N5352A * Then : VPin 9 0.75 Ipk 1 MC1555 Control Circuitry Ground (Pin 16) and Current Sense Inverting Input (Pin 15) * = MUR115 must return on separate paths to the Central Input Source Ground. 0.001 18 k VM = 170 V Virtually lossless current sensing can be achieved with the implementation of SENSEFET power switches. This circuit generates VBoost for Figure 25.

Figure 29. Current Sensing Power MOSFETs Figure 30. High Voltage Boost Supply

REF 8

REF Enable 7 25 μA 8 R1 11 7 25 μA Increase R2 EA R1 11 Speed 12 VA R 2 EA 13 PWM R3 12 C VB PWM R4 13

Resistor R1 with capacitor C sets the acceleration time constant while R2 R ) R R R 3 4 controls the deceleration. The values of R1 and R2 should be at least ten V + V ǒ Ǔ 2 * ǒ 4 V Ǔ Pin 13 A R ) R R R B times greater than the speed set potentiometer to minimize time constant 1 2 3 3 variations with different speed settings.

Figure 31. Differential Input Speed Controller Figure 32. Controlled Acceleration/Deceleration

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5.0 V 16 11 166 k V REF CC Q9 10 145 k 100 k 8 Q8 9 126 k Q7 12 7 108 k 7 25 μA REF P3 Q6 8 92.3 k 11 13 Q 6 BCD P2 5 To Sensor 14 5 77.6 k Inputs Q EA Input (Pin 4) μ P1 4 12 7 25 A 15 SN74LS145 4 63.6 k Q P0 3 13 PWM 11 3 51.3 k 0.01 10 k Q2 EA 2 40.4 k 100 k 12 Q1 1 10 k 1.0 M 13 PWM Gnd Q0 8 0.1 0.22 1.0 M

The SN74LS145 is an open collector BCD to One of Ten decoder. When con- The rotor position sensors can be used as a tachometer. By differentiating nected as shown, input codes 0000 through 1001 steps the PWM in incre- the positive−going edges and then integrating them over time, a voltage ments of approximately 10% from 0 to 90% on−time. Input codes 1010 proportional to speed can be generated. The error amp compares this volt- through 1111 will produce 100% on−time or full motor speed. age to that of the speed set to control the PWM.

Figure 33. Digital Speed Controller Figure 34. Closed Loop Speed Control

) R3 R4 R R V + V ǒ Ǔ 2 * ǒ 4 V Ǔ Pin 3 ref ) B R1 R2 R3 R3 REF 8 V V + ref B R R1 T 7 25 μA ǒ 5 )1Ǔ R 11 6 R5

R2 EA R3 12 R §§ R øR 3 5 6 PWM R6 R4 13

This circuit can control the speed of a cooling proportional to the difference between the sensor and set temperatures. The control loop is closed as the forced air cools the NTC thermistor. For controlled heating applications, ex- change the positions of R1 and R2.

Figure 35. Closed Loop Temperature Control

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SYSTEM APPLICATIONS Three Phase Motor Commutation spike reduction. Care must be taken in the selection of the The three phase application shown in Figure 36 is a bottom power switch transistors so that the current during full−featured open loop motor controller with full wave, six braking does not exceed the device rating. During braking, step drive. The upper power switch transistors are the peak current generated is limited only by the series Darlingtons while the lower devices are power MOSFETs. resistance of the conducting bottom switch and winding. Each of these devices contains an internal parasitic catch V ) EMF diode that is used to return the stator inductive energy back I + M peak R ) R to the power supply. The outputs are capable of driving a switch winding delta or wye connected stator, and a grounded neutral wye If the motor is running at maximum speed with no load, the if split supplies are used. At any given rotor position, only generated back EMF can be as high as the supply voltage, one top and one bottom power switch (of different totem and at the onset of braking, the peak current may approach poles) is enabled. This configuration switches both ends of twice the motor stall current. Figure 37 shows the the stator winding from supply to ground which causes the commutation waveforms over two electrical cycles. The current flow to be bidirectional or full wave. A leading edge first cycle (0° to 360°) depicts motor operation at full speed spike is usually present on the current waveform and can while the second cycle (360° to 720°) shows a reduced speed cause a current−limit instability. The spike can be eliminated with about 50% pulse width modulation. The current by adding an RC filter in series with the Current Sense Input. waveforms reflect a constant torque load and are shown Using a low type resistor for RS will also aid in synchronous to the commutation frequency for clarity.

V Fault M 14 Ind. 4

5 2 Q1 N 6 Rotor A S S 1 Position N Q2 3 Decoder Fwd/Rev 22 24 B 60°/120° Q3 C μ 7 25 A Enable 17 Undervoltage Motor VM Lockout 18

Reference Regulator 21 Q 8 4 Speed Set 11 Error Amp 20 Q Thermal 5 Faster 12 Shutdown PWM RT 13 R 19 Q Q 6 S 10 Oscillator S I CT Q Limit R 9 R

C RS 15

Gnd 16 23 Brake

Figure 36. Three Phase, Six Step, Full Wave Motor Controller

http://onsemi.com 18 MC33035, NCV33035

Rotor Electrical Position (Degrees)

0 60 120 180 240 300 360 420 480 540 600 660 720

SA

Sensor Inputs SB 60°/120° Select Pin Open SC

Code 100 110 111 011 001 000 100 110 111 011 001 000

SA

Sensor Inputs SB 60°/120° Select Pin Grounded SC

Code 100 110010011 001 101 100 110 010011 001 101

AT

Top Drive B Outputs T

CT

AB

Bottom Drive B Outputs B

CB

Conducting Power Switch Q1 + Q6 Q2 + Q6 Q2 + Q4 Q3 + Q4 Q3 + Q5 Q1 + Q5 Q1 + Q6 Q2 + Q6 Q2 + Q4 Q3 + Q4 Q3 + Q5 Q1 + Q5 Transistors

+ A O − + Motor Drive B O Current − + C O − Full Speed (No PWM) Reduced Speed ( ≈ 50% PWM)

Fwd/Rev = 1

Figure 37. Three Phase, Six Step, Full Wave Commutation Waveforms

http://onsemi.com 19 MC33035, NCV33035

Figure 38 shows a three phase, three step, half wave motor VM. A unique solution is to provide braking until the motor controller. This configuration is ideally suited for stops and then turn off the bottom drives. This can be automotive and other low voltage applications since there is accomplished by using the Fault Output in conjunction with only one power switch voltage drop in series with a given the Output Enable as an over current timer. Components stator winding. Current flow is unidirectional or half wave RDLY and CDLY are selected to give the motor sufficient time because only one end of each winding is switched. to stop before latching the Output Enable and the top drive Continuous braking with the typical half wave arrangement AND gates low. When enabling the motor, the brake switch presents a motor overheating problem since stator current is is closed and the PNP transistor (along with resistors R1 and limited only by the winding resistance. This is due to the lack RDLY) are used to reset the latch by discharging CDLY. The of upper power switch transistors, as in the full wave circuit, stator flyback voltage is clamped by a single zener and three used to disconnect the windings from the supply voltage diodes. Motor

C DLY R2 R1 R 14 DLY 4 N S S 5 2 N VM 6 Rotor Position Decoder 1 3 Fwd/Rev

22 60°/120° 24 μ 7 25 A

17 Undervoltage VM Lockout 18

Reference Regulator 21 8 Speed Set 11 Error Amp 20 Thermal Faster 12 Shutdown PWM RT 13 R Q 19 S 10 Oscillator S CT Q I R Limit 9 15

Gnd 16 23 Brake

Figure 38. Three Phase, Three Step, Half Wave Motor Controller

http://onsemi.com 20 MC33035, NCV33035

Three Phase Closed Loop Controller The MC33035, by itself, is only capable of open loop of pulses at Pin 5 of the MC33039 are integrated by the error motor speed control. For closed loop motor speed control, amplifier of the MC33035 configured as an integrator to the MC33035 requires an input voltage proportional to the produce a DC voltage level which is proportional to the motor speed. Traditionally, this has been accomplished by motor speed. This speed proportional voltage establishes the means of a tachometer to generate the motor speed feedback PWM reference level at Pin 13 of the MC33035 motor voltage. Figure 39 shows an application whereby an controller and closes the feedback loop. The MC33035 MC33039, powered from the 6.25 V reference (Pin 8) of the outputs drive a TMOS power MOSFET 3−phase bridge. MC33035, is used to generate the required feedback voltage High currents can be expected during conditions of start−up, without the need of a costly tachometer. The same Hall breaking, and change of direction of the motor. sensor signals used by the MC33035 for rotor position The system shown in Figure 39 is designed for a motor decoding are utilized by the MC33039. Every positive or having 120/240 degrees Hall sensor electrical phasing. The negative going transition of the Hall sensor signals on any system can easily be modified to accommodate 60/300 of the sensor lines causes the MC33039 to produce an output degree Hall sensor electrical phasing by removing the pulse of defined amplitude and time duration, as determined jumper (J2) at Pin 22 of the MC33035. by the external resistor R1 and capacitor C1. The output train

1 8 2 7 1.0 M MC33039 R1 VM (18 to 30 V) 3 6 750 pF 4 5 C1 0.1 1000 1.1 k 1.1 k 1.1 k TP1 1.0 k 1.0 k 1.0 k N 1 24 S 2 23 Brake S F/R N 3 22 J2 470 4 21 470 5 20 MC33035 470 6 19 7 18 Motor 4.7 k 1N5819 8 17 Enable J1 5.1 k 9 16 330 2.2 k

10 15 Fault TP 0.01 1N5355B 0.1 2 Speed 11 14 18 V 100 12 13 Faster 0.05/1.0 W 1.0 M 10 k 1N4148 0.1 33 0.1 2.2 k Reset 100 k Close Loop Latch On Fault 47 μF

Figure 39. Closed Loop Brushless DC Motor Control Using The MC33035 and MC33039

http://onsemi.com 21 MC33035, NCV33035

Sensor Phasing Comparison There are four conventions used to establish the relative In this data sheet, the rotor position is always given in phasing of the sensor signals in three phase motors. With six electrical degrees since the mechanical position is a function step drive, an input signal change must occur every 60 of the number of rotating magnetic poles. The relationship electrical degrees; however, the relative signal phasing is between the electrical and mechanical position is: dependent upon the mechanical sensor placement. A #Rotor Poles Electrical Degrees + Mechanical Degreesǒ Ǔ comparison of the conventions in electrical degrees is shown 2 in Figure 40. From the sensor phasing table in Figure 41, An increase in the number of magnetic poles causes more note that the order of input codes for 60° phasing is the electrical revolutions for a given mechanical revolution. reverse of 300°. This means the MC33035, when configured General purpose three phase motors typically contain a four for 60° sensor electrical phasing, will operate a motor with pole rotor which yields two electrical revolutions for one either 60° or 300° sensor electrical phasing, but resulting in mechanical. opposite directions of rotation. The same is true for the part when it is configured for 120° sensor electrical phasing; the Two and Four Phase Motor Commutation motor will operate equally, but will result in opposite The MC33035 is also capable of providing a four step directions of rotation for 120° for 240° conventions. output that can be used to drive two or four phase motors. The truth table in Figure 42 shows that by connecting sensor Rotor Electrical Position (Degrees) inputs SB and SC together, it is possible to truncate the 0 60 120 180 240 300 360 420 480 540 600 660 720 number of drive output states from six to four. The output power switches are connected to BT, CT, BB, and CB. SA Figure 43 shows a four phase, four step, full wave motor ° control application. Power switch transistors Q through Q 60 SB 1 8 are Darlington type, each with an internal parasitic catch SC diode. With four step drive, only two rotor position sensors SA spaced at 90 electrical degrees are required. The ° commutation waveforms are shown in Figure 44. 120 SB Figure 45 shows a four phase, four step, half wave motor S C controller. It has the same features as the circuit in Figure 38,

SA except for the deletion of speed control and braking.

240° SB Sensor Electrical Phasing ° ° SC MC33035 (60 /120 Select Pin Open) Inputs Outputs SA Sensor Electrical Top Drives Bottom Drives 300° S B Spacing* = 90° S C SA SB F/R BT CT BB CB 1 0 1 1 1 0 1 1 1 1 0 1 0 0 Figure 40. Sensor Phasing Comparison 0 1 1 1 0 0 0 0 0 1 1 1 1 0 1 0 0 1 0 0 0 Sensor Electrical Phasing (Degrees) 1 1 0 1 1 1 0 0 1 0 1 1 0 1 60° 120° 240° 300° 0 0 0 0 1 0 0 S S S S S S S S S S S S A B C A B C A B C A B C *With MC33035 sensor input SB connected to SC. 1 0 0 1 0 1 1 1 0 1 1 1 Figure 42. Two and Four Phase, Four Step, 1 1 0 1 0 0 1 0 0 1 1 0 Commutation Truth Table 1 1 1 1 1 0 1 0 1 1 0 0 0 1 1 0 1 0 0 0 1 0 0 0 0 0 1 0 1 1 0 1 1 0 0 1 0 0 0 0 0 1 0 1 0 0 1 1 Figure 41. Sensor Phasing Table

http://onsemi.com 22 MC33035, NCV33035 S N Motor N S A B C D 1 5 Q Q 2 6 Q Q S R 3 7 M Q Q V 4 8 Q Q R Ind. Fault C 9 2 1 24 21 20 19 14 15 Limit I 23 Q Q Rotor Position Decoder S R R S Gnd 16 Thermal Shutdown Lockout Undervoltage PWM μ 25 A 25 Oscillator Error Amp Regulator Reference 4 5 6 3 7 8 11 17 12 13 18 10 22 M V Enable T T Fwd/Rev C R

Figure 43. Four Phase, Four Step, Full Wave Motor Controller

http://onsemi.com 23 MC33035, NCV33035

Rotor Electrical Position (Degrees)

090180 270 360 450 540 630 720

SA Sensor Inputs 60°/120° S Select Pin B Open Code 10 10 01 00 10 11 01 00

BT Top Drive Outputs CT

BB Bottom Drive Outputs CB Conducting Power Switch Q3 + Q5 Q4 + Q6 Q1 + Q7 Q2 + Q8 Q3 + Q5 Q4 + Q6 Q1 + Q7 Q2 + Q8 Transistors

+ A O − +

B O Motor Drive - Current + C O − + D O −

Full Speed (No PWM) Fwd/Rev = 1

Figure 44. Four Phase, Four Step, Full Wave Motor Controller

http://onsemi.com 24 MC33035, NCV33035 N S S N Motor M V S R R Ind. Fault C 9 2 1 24 14 21 20 19 15 Limit I Brake 23 Q Q Rotor Position Decoder S R R S Gnd 16 Thermal Shutdown Lockout Undervoltage PWM μ 25 A 25 Oscillator Error Amp Regulator Reference 4 5 6 3 7 8 11 17 18 12 13 10 22 M V Enable T Fwd/Rev T C R

Figure 45. Four Phase, Four Step, Half Wave Motor Controller

http://onsemi.com 25 MC33035, NCV33035

Brush Motor Control makes it possible to reverse the direction of the motor, using Though the MC33035 was designed to control brushless the normal forward/reverse switch, on the fly and not have DC motors, it may also be used to control DC brush type to completely stop before reversing. motors. Figure 46 shows an application of the MC33035 driving a MOSFET H−bridge affording minimal parts count LAYOUT CONSIDERATIONS to operate a brush−type motor. Key to the operation is the Do not attempt to construct any of the brushless motor input sensor code [100] which produces a top−left (Q1) and control circuits on wire−wrap or plug−in prototype a bottom−right (Q3) drive when the controller’s boards. High frequency printed circuit layout techniques forward/reverse pin is at logic [1]; top−right (Q4), bottom−left are imperative to prevent pulse jitter. This is usually caused (Q2) drive is realized when the Forward/Reverse pin is at by excessive noise pick−up imposed on the current sense or logic [0]. This code supports the requirements necessary for error amp inputs. The printed circuit layout should contain H−bridge drive accomplishing both direction and speed a ground plane with low current signal and high drive and control. output buffer grounds returning on separate paths back to the The controller functions in a normal manner with a pulse power supply input filter capacitor VM. Ceramic bypass width modulated frequency of approximately 25 kHz. capacitors (0.1 μF) connected close to the integrated circuit Motor speed is controlled by adjusting the voltage presented at VCC, VC, Vref and the error amp noninverting input may to the noninverting input of the error amplifier establishing be required depending upon circuit layout. This provides a the PWM’s slice or reference level. Cycle−by−cycle current low impedance path for filtering any high frequency noise. limiting of the motor current is accomplished by sensing the All high current loops should be kept as short as possible voltage (100 mV) across the RS resistor to ground of the using heavy copper runs to minimize radiated EMI. H−bridge motor current. The over current sense circuit

http://onsemi.com 26 MC33035, NCV33035

Fault +12 V 14 Ind. 4 20 k

5 2 1.0 k

6 Rotor Position 1.0 k Decoder 1 3 Q1* Fwd/Rev

22 24 25 μA Q * Enable 7 4 17 Undervoltage +12 V Lockout 18 DC Brush M Motor

Reference Regulator 21 Q2* 8 22

11 Error Amp 10 k 20 Thermal Faster 12 Shutdown PWM 10 k 13 R Q * Q 19 3 S 22 10 Oscillator S 0.005 Q ILimit R 9 1.0 k 15 0.001 RS

Gnd 16 23 Brake

Figure 46. H−Bridge Brush−Type Controller

http://onsemi.com 27 MC33035, NCV33035

ORDERING INFORMATION

Device Operating Temperature Range Package Shipping† MC33035DWG SOIC−24 WB 30 Units / Rail (Pb−Free) MC33035DWR2G SOIC−24 WB 1000 Tape & Reel T = −40°C to +85°C A (Pb−Free) MC33035PG PDIP−24 15 Units / Tube (Pb−Free) NCV33035DWR2* SOIC−24 WB 1000 Tape & Reel ° ° NCV33035DWR2G* TA = −40 C to +125 C SOIC−24 WB 1000 Tape & Reel (Pb−Free) †For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specification Brochure, BRD8011/D. *NCV33035: Tlow = −40C, Thigh = +125C. Guaranteed by design. NCV prefix for automotive and other applications requiring unique site and control change requirements; AEC−Q100 Qualified and PPAP Capable.

MARKING DIAGRAMS

SO−24 PDIP−24 DW SUFFIX P SUFFIX CASE 751E CASE 724 24 24

MC33035P MC33035DW AWLYYWWG AWLYYWWG 1

1

24 A = Assembly Location WL = Wafer Lot YY = Year WW = Work Week NCV33035DW G = Pb−Free Package AWLYYWWG

1

http://onsemi.com 28 MC33035, NCV33035

PACKAGE DIMENSIONS

PDIP−24 CASE 724−03 ISSUE D -A- NOTES: 1. CHAMFERED CONTOUR OPTIONAL. 24 13 2. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. -B- 3. DIMENSIONING AND TOLERANCING PER ANSI 112 Y14.5M, 1982. 4. CONTROLLING DIMENSION: INCH.

INCHES MILLIMETERS L DIM MINMAX MIN MAX C A 1.230 1.265 31.25 32.13 B 0.250 0.270 6.35 6.85 C 0.145 0.175 3.69 4.44 -T- K NOTE 1 D 0.015 0.020 0.38 0.51 SEATING E 0.050 BSC 1.27 BSC PLANE N M F 0.040 0.060 1.02 1.52 E G 0.100 BSC 2.54 BSC G F J 24 PL J 0.007 0.012 0.18 0.30 K 0.110 0.140 2.80 3.55 M M D 24 PL 0.25 (0.010) T B L 0.300 BSC 7.62 BSC M 0° 15° 0° 15° 0.25 (0.010)M T A M N 0.020 0.040 0.51 1.01

http://onsemi.com 29 MC33035, NCV33035

PACKAGE DIMENSIONS

SOIC−24 WB CASE 751E−04 ISSUE F

NOTES: 1. DIMENSIONING AND TOLERANCING PER ASME H Y14.5M, 1994. D A 2. CONTROLLING DIMENSION: MILLIMETERS. B 3. DIMENSIONS b AND c APPLY TO THE FLAT SEC- 0.25 C TION OF THE LEAD AND ARE MEASURED BE- TWEEN 0.10 AND 0.25 FROM THE LEAD TIP. 24 13 4. DIMENSIONS D AND E1 DO NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL E E1 NOT EXCEED 0.15 mm PER SIDE. INTERLEAD 1 L C FLASH OR PROTRUSION SHALL NOT EXCEED 12 0.25 PER SIDE. DIMENSIONS D AND E1 ARE DETAIL A DETERMINED AT DATUM H. 5. A1 IS DEFINED AS THE VERTICAL DISTANCE 24X b FROM THE SEATING PLANE TO THE LOWEST POINT ON THE PACKAGE BODY. PIN 1 INDICATOR 0.25 M C A S B S MILLIMETERS TOP VIEW NOTE 3 DIM MIN MAX A 2.35 2.65 h _ A1 0.13 0.29 A x 45 b 0.35 0.49 M c 0.23 0.32 D 15.25 15.54 E 10.30 BSC c E1 7.40 7.60 A1 e SEATING DETAIL A e 1.27 BSC C PLANE NOTE 3 NOTE 5 h 0.25 0.75 SIDE VIEW END VIEW L 0.41 0.90 M 0 _ 8 _ RECOMMENDED SOLDERING FOOTPRINT* 24X 24X 0.52 1.62

11.00

1 1.27 PITCH DIMENSIONS: MILLIMETERS *For additional information on our Pb−Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.

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