EE C128 Chapter 10

Total Page:16

File Type:pdf, Size:1020Kb

EE C128 Chapter 10 Lecture abstract EE C128 / ME C134 – Feedback Control Systems Topics covered in this presentation Lecture – Chapter 10 – Frequency Response Techniques I Advantages of FR techniques over RL I Define FR Alexandre Bayen I Define Bode & Nyquist plots I Relation between poles & zeros to Bode plots (slope, etc.) Department of Electrical Engineering & Computer Science st nd University of California Berkeley I Features of 1 -&2 -order system Bode plots I Define Nyquist criterion I Method of dealing with OL poles & zeros on imaginary axis I Simple method of dealing with OL stable & unstable systems I Determining gain & phase margins from Bode & Nyquist plots I Define static error constants September 10, 2013 I Determining static error constants from Bode & Nyquist plots I Determining TF from experimental FR data Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 1 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 2 / 64 10 FR techniques 10.1 Intro Chapter outline 1 10 Frequency response techniques 1 10 Frequency response techniques 10.1 Introduction 10.1 Introduction 10.2 Asymptotic approximations: Bode plots 10.2 Asymptotic approximations: Bode plots 10.3 Introduction to Nyquist criterion 10.3 Introduction to Nyquist criterion 10.4 Sketching the Nyquist diagram 10.4 Sketching the Nyquist diagram 10.5 Stability via the Nyquist diagram 10.5 Stability via the Nyquist diagram 10.6 Gain margin and phase margin via the Nyquist diagram 10.6 Gain margin and phase margin via the Nyquist diagram 10.7 Stability, gain margin, and phase margin via Bode plots 10.7 Stability, gain margin, and phase margin via Bode plots 10.8 Relation between closed-loop transient and closed-loop 10.8 Relation between closed-loop transient and closed-loop frequency responses frequency responses 10.9 Relation between closed- and open-loop frequency responses 10.9 Relation between closed- and open-loop frequency responses 10.10 Relation between closed-loop transient and open-loop 10.10 Relation between closed-loop transient and open-loop frequency responses frequency responses 10.11 Steady-state error characteristics from frequency response 10.11 Steady-state error characteristics from frequency response 10.12 System with time delay 10.12 System with time delay 10.13 Obtaining transfer functions experimentally 10.13 Obtaining transfer functions experimentally Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 3 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 4 / 64 10 FR techniques 10.1 Intro 10 FR techniques 10.1 Intro Advantages of frequency response (FR) methods, [1, p. The concept of FR, [1, p. 535] 534] I At steady-state, sinusoidal inputs to a linear system generate sinusoidal responses In the following situations of the same frequency with I When modeling TFs from physical data di↵erent amplitudes and phase I When designing lead compensators to meet a steady-state error angle from the input, each of requirements which are a function of frequency. I When finding the stability of NL systems I Phasor – complex I In settling ambiguities when sketching a root locus representation of a sinusoid I G(!) – amplitude || || I \G(!) – phase angle Figure: Sinusoidal FR: a. system; b. I M cos(!t + φ) ... M\φ TF; c. IO waveforms Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 5 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 6 / 64 10 FR techniques 10.1 Intro 10 FR techniques 10.1 Intro The concept of FR, [1, p. 535] Analytical expressions for FR, [1, p. 536] I Steady-state output sinusoid I General input sinusoid Mo(!)\φo(!) r(t)=A cos(!t)+B sin(!t) = Mi(!)M(!)\(φi(!)+φ(!)) 2 2 1 B = A + B cos !t tan− A I Magnitude FR − p I Input phasor forms Mo(!) M(!)= I Polar, Mi\φi Mi(!) Figure: System with 2 2 Mi = A + B sinusoidal input I Phase FR p 1 B φ = tan− i − A φ(!)=φo(!) φi(!) − I Rectangular, A jB jφ − Figure: Sinusoidal FR: a. system; b. I Euler’s, M e i I FR i TF; c. IO waveforms M(!)\φ(!) Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 7 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 8 / 64 10 FR techniques 10.1 Intro 10 FR techniques 10.2 Asymptotic approximations: Bode plots Analytical expressions for FR, [1, p. 536] 1 10 Frequency response techniques 10.1 Introduction I Forced response 10.2 Asymptotic approximations: Bode plots As + B! C(s)= G(s) 10.3 Introduction to Nyquist criterion s2 + !2 10.4 Sketching the Nyquist diagram I Steady-state forced response after partial fraction expansion 10.5 Stability via the Nyquist diagram MiMG j(φ φ ) MiMG j(φ φ ) e− i− G e i− G 10.6 Gain margin and phase margin via the Nyquist diagram C (s)= 2 + 2 ss s + j! s j! 10.7 Stability, gain margin, and phase margin via Bode plots − 10.8 Relation between closed-loop transient and closed-loop where MG = G(j!) and φG = \G(j!) || || frequency responses I Time-domain response 10.9 Relation between closed- and open-loop frequency responses c(t)=MiMG cos(!t + φi + φG) 10.10 Relation between closed-loop transient and open-loop I Time-domain response in phasor form frequency responses 10.11 Steady-state error characteristics from frequency response Mo\φo =(Mi\φi)(MG\φG) 10.12 System with time delay I FR of system 10.13 Obtaining transfer functions experimentally G(j!)=G(s) s j! | ! Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 9 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 10 / 64 10 FR techniques 10.2 Asymptotic approximations: Bode plots 10 FR techniques 10.2 Asymptotic approximations: Bode plots History interlude General Bode plots, [1, p. 540] History (Hendrik Wade Bode) I 1905 – 1982 I American engineer I 1930s – Inventor of Bode plots, gain margin, & phase margin G(j!)=MG(!)\φG(!) I 1944 – WWII anti-aircraft (including V-1 flying bombs) I Separate magnitude and phase plots as a function of frequency systems I Magnitude – decibels (dB)vs.log(!),wheredB = 20 log(M) I Phase – phase angle vs. log(!) I 1947 – Cold War anti-ballistic missiles I 1957 – Served on NACA (now NASA) with Wernher von Braun (inventor of V-1 flying Figure: Hendrik Wade Bode bombs & V-2 rockets) Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 11 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 12 / 64 10 FR techniques 10.2 Asymptotic approximations: Bode plots 10 FR techniques 10.2 Asymptotic approximations: Bode plots Bode plots approximations, [1, p. 542] Simple Bode plots, [1, p. 542] I TF G(s)=s + a 40 0 I Low frequencies 30 −10 20 −20 G(j!) a 0◦ Magnitude (dB) ⇡ \ Magnitude (dB) 10 −30 0 −40 I High frequencies 90 0 60 −30 G(j!) ! 90◦ \ 30 −60 Phase (deg) ⇡ Phase (deg) 0 −90 I Asymptotes – straight-line −2 −1 0 1 2 −2 −1 0 1 2 10 10 10 10 10 10 10 10 10 10 approximations Frequency (Hz) Frequency (Hz) I Low-frequency Figure: Bode plots of s + a:a. Figure: Bode plot of s+a Figure: Bode plot of a I Break frequency magnitude plot; b. phase plot a s+a I High-frequency Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 13 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 14 / 64 10 FR techniques 10.2 Asymptotic approximations: Bode plots 10 FR techniques 10.2 Asymptotic approximations: Bode plots Simple Bode plots, [1, p. 545] Simple Bode plots, [1, p. 549] 80 0 30 0 60 −20 20 −10 40 −40 10 −20 Magnitude (dB) Magnitude (dB) Magnitude (dB) 20 −60 Magnitude (dB) 0 −30 0 −80 91 −89 180 0 90.8 −89.2 90.6 −89.4 135 −45 90.4 −89.6 90.2 −89.8 90 −90 90 −90 89.8 −90.2 −90.4 Phase (deg) Phase (deg) 89.6 Phase (deg) Phase (deg) 45 −135 89.4 −90.6 89.2 −90.8 89 −91 0 −180 −1 0 1 −1 0 1 −2 −1 0 1 2 −2 −1 0 1 2 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 10 Frequency (Hz) Frequency (Hz) Frequency (Hz) Frequency (Hz) 2 2 2 1 s +2⇣!ns+!n !n Figure: Bode plot of s Figure: Bode plot of Figure: Bode plot of 2 Figure: Bode plot of 2 2 s !n s +2⇣!ns+!n Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 15 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 16 / 64 10 FR techniques 10.2 Asymptotic approximations: Bode plots 10 FR techniques 10.3 Intro to Nyquist criterion nd Detailed 2 -order Bode plots, [1, p. 550] 1 10 Frequency response techniques 10.1 Introduction 10.2 Asymptotic approximations: Bode plots 10.3 Introduction to Nyquist criterion 10.4 Sketching the Nyquist diagram 10.5 Stability via the Nyquist diagram 10.6 Gain margin and phase margin via the Nyquist diagram 10.7 Stability, gain margin, and phase margin via Bode plots 10.8 Relation between closed-loop transient and closed-loop frequency responses 10.9 Relation between closed- and open-loop frequency responses 10.10 Relation between closed-loop transient and open-loop frequency responses 10.11 Steady-state error characteristics from frequency response 10.12 System with time delay 2 2 !2 s +2⇣!ns+!n n Figure: Bode plot of 2 Figure: Bode plot of s2+2⇣! s+!2 10.13 Obtaining transfer functions experimentally !n n n Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 17 / 64 Bayen (EECS, UCB) Feedback Control Systems September 10, 2013 18 / 64 10 FR techniques 10.3 Intro to Nyquist criterion 10 FR techniques 10.3 Intro to Nyquist criterion History interlude Introduction, [1, p.
Recommended publications
  • Lesson 22: Determining Control Stability Using Bode Plots
    11/30/2015 Lesson 22: Determining Control Stability Using Bode Plots 1 ET 438A AUTOMATIC CONTROL SYSTEMS TECHNOLOGY lesson22et438a.pptx Learning Objectives 2 After this presentation you will be able to: List the control stability criteria for open loop frequency response. Identify the gain and phase margins necessary for a stable control system. Use a Bode plot to determine if a control system is stable or unstable. Generate Bode plots of control systems the include dead-time delay and determine system stability. lesson22et438a.pptx 1 11/30/2015 Bode Plot Stability Criteria 3 Open loop gain of less than 1 (G<1 or G<0dB) at Stable Control open loop phase angle of -180 degrees System Oscillatory Open loop gain of exactly 1 (G=1 or G= 0dB) at Control System open loop phase angle of -180 degrees Marginally Stable Unstable Control Open loop gain of greater than 1 (G>1 or G>0dB) System at open loop phase angle of -180 degrees lesson22et438a.pptx Phase and Gain Margins 4 Inherent error and inaccuracies require ranges of phase shift and gain to insure stability. Gain Margin – Safe level below 1 required for stability Minimum level : G=0.5 or -6 dB at phase shift of 180 degrees Phase Margin – Safe level above -180 degrees required for stability Minimum level : f=40 degree or -180+ 40=-140 degrees at gain level of 0.5 or 0 dB. lesson22et438a.pptx 2 11/30/2015 Determining Phase and Gain Margins 5 Define two frequencies: wodB = frequency of 0 dB gain w180 = frequency of -180 degree phase shift Open Loop Gain 0 dB Gain Margin -m180 bodB Phase Margin -180+b0dB -180o Open Loop w w Phase odB 180 lesson22et438a.pptx Determining Phase and Gain Margins 6 Procedure: 1) Draw vertical lines through 0 dB on gain and -180 on phase plots.
    [Show full text]
  • Op Amp Stability and Input Capacitance
    Amplifiers: Op Amps Texas Instruments Incorporated Op amp stability and input capacitance By Ron Mancini (Email: [email protected]) Staff Scientist, Advanced Analog Products Introduction Figure 1. Equation 1 can be written from the op Op amp instability is compensated out with the addition of amp schematic by opening the feedback loop an external RC network to the circuit. There are thousands and calculating gain of different op amps, but all of them fall into two categories: uncompensated and internally compensated. Uncompen- sated op amps always require external compensation ZG ZF components to achieve stability; while internally compen- VIN1 sated op amps are stable, under limited conditions, with no additional external components. – ZG VOUT Internally compensated op amps can be made unstable VIN2 + in several ways: by driving capacitive loads, by adding capacitance to the inverting input lead, and by adding in ZF phase feedback with external components. Adding in phase feedback is a popular method of making an oscillator that is beyond the scope of this article. Input capacitance is hard to avoid because the op amp leads have stray capaci- tance and the printed circuit board contributes some stray Figure 2. Open-loop-gain/phase curves are capacitance, so many internally compensated op amp critical stability-analysis tools circuits require external compensation to restore stability. Output capacitance comes in the form of some kind of load—a cable, converter-input capacitance, or filter 80 240 VDD = 1.8 V & 2.7 V (dB) 70 210 capacitance—and reduces stability in buffer configurations. RL= 2 kΩ VD 60 180 CL = 10 pF 150 Stability theory review 50 TA = 25˚C 40 120 Phase The theory for the op amp circuit shown in Figure 1 is 90 β 30 taken from Reference 1, Chapter 6.
    [Show full text]
  • Control Engineering for High School Students and Teachers: an Online Platform Development
    Control Engineering for High School Students and Teachers: An Online Platform Development Farhad Farokhi and Iman Shames Contents Report ............................................ 1 1 Introduction . 1 2 Courses . 1 3 Interviews . 2 4 Educational games . 3 5 Remote laboratory . 4 6 Conclusions and future work . 5 Appendix .......................................... 6 A Example course 1: Feedback theory . 6 B Example course 2: Models . 9 C Example course 3: On/off control . 12 D Remote laboratory (RLAB) manual . 13 1 Introduction Based on our teen years and feedback from many of our colleagues and friends, we believe that the control engineering, although being a major building block of automated system in many processes and infrastructures, is a fairly alien subject to the students, parents, and teachers. Therefore, there is a need for introducing feedback control and its application to high school students and their teachers to recruit the next generation of engineers and scientists in this field. We also believe that the academic community has a responsibility to disseminate the information cheaply, if not freely, to a wide range of interested audience, be it students, parents, or teachers, across the globe. This way, we can guarantee that people from different socio- economic backgrounds and in different countries can make informed decisions regarding their careers and those of their friends and families. Motivated by these needs, in this project, we have attempted at developing an online platform for the students and their educators to read about the control engineering, watch lectures by researchers from academia and industry, access interviews with successful people in the control engineering community, and play online games to test their understanding and to possibly learn about the applications of the automatic control.
    [Show full text]
  • Download Chapter 161KB
    Memorial Tributes: Volume 3 HENDRIK WADE BODE 50 Copyright National Academy of Sciences. All rights reserved. Memorial Tributes: Volume 3 HENDRIK WADE BODE 51 Hendrik Wade Bode 1905–1982 By Harvey Brooks Hendrik Wade Bode was widely known as one of the most articulate, thoughtful exponents of the philosophy and practice of systems engineering—the science and art of integrating technical components into a coherent system that is optimally adapted to its social function. After a career of more than forty years with Bell Telephone Laboratories, which he joined shortly after its founding in 1926, Dr. Bode retired in 1967 to become Gordon McKay Professor of Systems Engineering (on a half-time basis) in what was then the Division of Engineering and Applied Physics at Harvard. He became professor emeritus in July 1974. He died at his home in Cambridge on June 21, 1982, at the age of seventy- six. He is survived by his wife, Barbara Poore Bode, whom he married in 1933, and by two daughters, Dr. Katharine Bode Darlington of Philadelphia and Mrs. Anne Hathaway Bode Aarnes of Washington, D.C. Hendrik Bode was born in Madison, Wisconsin, on December 24, 1905. After attending grade school in Tempe, Arizona, and high school in Urbana, Illinois, he went on to Ohio State University, from which he received his B.A. in 1924 and his M.A. in 1926, both in mathematics. He joined Bell Labs in 1926 to work on electrical network theory and the design of electric filters. While at Bell, he also pursued graduate studies at Columbia University, receiving his Ph.D.
    [Show full text]
  • I Introduction and Background
    Final Design Report Platform Motion Measurement System ELEC 492 A Senior Design Project, 2005 Between University of San Diego And Trex Enterprises Submitted to: Dr. Lord at USD Prepared by: YAZ Zlatko Filipovic Yoshitaka Yano August 12, 2005 University of San Diego Final Design Report USD August 12, 2005 Platform Motion Measurement System Table of Contents I. Acknowledgments…………...…………………………………………………………4 II. Executive Summary……..…………………………………………………………….5 III. Introduction and Background…...………………………...………………………….6 IV. Project Requirements…………….................................................................................8 V. Methodology of Design Plan……….…..……………..…….………….…..…….…..11 VI. Testing….……………………………………..…..…………………….……...........21 VII. Deliverables and Project Results………...…………...…………..…….…………...24 VIII. Budget………………………………………...……..……………………………..25 IX. Personnel…………………..………………………………………....….……….......28 X. Design Schedule………….…...……………………………….……...…………........29 XI. Reference and Bibliography…………..…………..…………………...…………….31 XII. Summary…………………………………………………………………………....32 Appendices Appendix 1. Simulink Simulations…..………………………….…….33 Appendix 2. VisSim Simulations..........……………………………….34 Appendix 3. Frequency Response and VisSim results……………......36 Appendix 4. Vibration Measurements…………..………………….….38 Appendix 5. PCB Layout and Schematic……………………………..39 Appendix 6. User’s Manual…………………………………………..41 Appendix 7. PSpice Simulations of Hfilter…………………………….46 1 Final Design Report USD August 12, 2005 Platform Motion Measurement System
    [Show full text]
  • Meeting Design Specifications
    NDSU Meeting Design Specs using Bode Plots ECE 461 Meeting Design Specs using Bode Plots When designing a compensator to meet design specs including: Steady-state error for a step input Phase Margin 0dB gain frequency the procedure using Bode plots is about the same as it was for root-locus plots. Add a pole at s = 0 if needed (making the system type-1) Start cancelling zeros until the system is too fast For every zero you added, add a pole. Place these poles so that the phase adds up. When using root-locus techniques, the phase adds up to 180 degrees at some spot on the s-plane. When using Bode plot techniques, the phase adds up to give you your phase margin at some spot on the jw axis. Example 1: Problem: Given the following system 1000 G(s) = (s+1)(s+3)(s+6)(s+10) Design a compensator which result in No error for a step input 20% overshoot for a step input, and A settling time of 4 second Solution: First, convert to Bode Plot terminology No overshoot means make this a type-1 system. Add a pole at s = 0. 20% overshoot means ζ = 0.4559 Mm = 1.2322 GK = 1∠ − 132.120 Phase Margin = 47.88 degrees A settling time of 4 seconds means s = -1 + j X s = -1 + j2 (from the damping ratio) The 0dB gain frequency is 2.00 rad/sec In short, design K(s) so that the system is type-1 and 0 (GK)s=j2 = 1∠ − 132.12 JSG 1 rev June 22, 2016 NDSU Meeting Design Specs using Bode Plots ECE 461 Start with s+1 K(s) = s At 4 rad/sec 1000 0 GK = s(s+3)(s+6)(s+10) = 2.1508∠ − 153.43 s=j2 There is too much phase shift, so start cancelling zeros.
    [Show full text]
  • Applications Academic Program Distributing Vissim Models
    VISSIM VisSim is a visual block diagram language for simulation of dynamical systems and Model Based Design of embedded systems. It is developed by Visual Solutions of Westford, Massachusetts. Applications VisSim is widely used in control system design and digital signal processing for multidomain simulation and design. It includes blocks for arithmetic, Boolean, and transcendental functions, as well as digital filters, transfer functions, numerical integration and interactive plotting. The most commonly modeled systems are aeronautical, biological/medical, digital power, electric motor, electrical, hydraulic, mechanical, process, thermal/HVAC and econometric. Academic program The VisSim Free Academic Program allows accredited educational institutions to site license VisSim v3.0 for no cost. The latest versions of VisSim and addons are also available to students and academic institutions at greatly reduced pricing. Distributing VisSim models VisSim viewer screenshot with sample model. The free Vis Sim Viewer is a convenient way to share VisSim models with colleagues and clients not licensed to use VisSim. The VisSim Viewer will execute any VisSim model, and allows changes to block and simulation parameters to illustrate different design scenarios. Sliders and buttons may be activated if included in the model. Code generation The VisSim/C-Code add-on generates efficient, readable ANSI C code for algorithm acceleration and real-time implementation of embedded systems. The code is more efficient and readable than most other code generators. VisSim's author served on the X3J11 ANSI C committee and wrote several C compilers, in addition to co-authoring a book on C. [2] This deep understanding of ANSI C, and the nature of the resulting machine code when compiled, is the key to the code generator's efficiency.
    [Show full text]
  • OA-25 Stability Analysis of Current Feedback Amplifiers
    OBSOLETE Application Report SNOA371C–May 1995–Revised April 2013 OA-25 Stability Analysis of Current Feedback Amplifiers ..................................................................................................................................................... ABSTRACT High frequency current-feedback amplifiers (CFA) are finding a wide acceptance in more complicated applications from dc to high bandwidths. Often the applications involve amplifying signals in simple resistive networks for which the device-specific data sheets provide adequate information to complete the task. Too often the CFA application involves amplifying signals that have a complex load or parasitic components at the external nodes that creates stability problems. Contents 1 Introduction .................................................................................................................. 2 2 Stability Review ............................................................................................................. 2 3 Review of Bode Analysis ................................................................................................... 2 4 A Better Model .............................................................................................................. 3 5 Mathematical Justification .................................................................................................. 3 6 Open Loop Transimpedance Plot ......................................................................................... 4 7 Including Z(s) ...............................................................................................................
    [Show full text]
  • Frequency Response and Bode Plots
    1 Frequency Response and Bode Plots 1.1 Preliminaries The steady-state sinusoidal frequency-response of a circuit is described by the phasor transfer function Hj( ) . A Bode plot is a graph of the magnitude (in dB) or phase of the transfer function versus frequency. Of course we can easily program the transfer function into a computer to make such plots, and for very complicated transfer functions this may be our only recourse. But in many cases the key features of the plot can be quickly sketched by hand using some simple rules that identify the impact of the poles and zeroes in shaping the frequency response. The advantage of this approach is the insight it provides on how the circuit elements influence the frequency response. This is especially important in the design of frequency-selective circuits. We will first consider how to generate Bode plots for simple poles, and then discuss how to handle the general second-order response. Before doing this, however, it may be helpful to review some properties of transfer functions, the decibel scale, and properties of the log function. Poles, Zeroes, and Stability The s-domain transfer function is always a rational polynomial function of the form Ns() smm as12 a s m asa Hs() K K mm12 10 (1.1) nn12 n Ds() s bsnn12 b s bsb 10 As we have seen already, the polynomials in the numerator and denominator are factored to find the poles and zeroes; these are the values of s that make the numerator or denominator zero. If we write the zeroes as zz123,, zetc., and similarly write the poles as pp123,, p , then Hs( ) can be written in factored form as ()()()s zsz sz Hs() K 12 m (1.2) ()()()s psp12 sp n 1 © Bob York 2009 2 Frequency Response and Bode Plots The pole and zero locations can be real or complex.
    [Show full text]
  • Chapter 6 Amplifiers with Feedback
    ELECTRONICS-1. ZOLTAI CHAPTER 6 AMPLIFIERS WITH FEEDBACK Purpose of feedback: changing the parameters of the amplifier according to needs. Principle of feedback: (S is the symbol for Signal: in the reality either voltage or current.) So = AS1 S1 = Si - Sf = Si - ßSo Si S1 So = A(Si - S ) So ß o + A from where: - Sf=ßSo * So A A ß A = Si 1 A 1 H where: H = Aß Denominations: loop-gain H = Aß open-loop gain A = So/S1 * closed-loop gain A = So/Si Qualitatively different cases of feedback: oscillation with const. amplitude oscillation with narrower growing amplitude pos. f.b. H -1 0 positive feedback negative feedback Why do we use almost always negative feedback? * The total change of the A as a function of A and ß: 1(1 A) A A 2 A* = A (1 A) 2 (1 A) 2 Introducing the relative errors: A * 1 A A A * 1 A A 1 A According to this, the relative error of the open loop gain will be decreased by (1+Aß), and the error of the feedback circuit goes 1:1 into the relative error of the closed loop gain. This is the Elec1-fb.doc 52 ELECTRONICS-1. ZOLTAI reason for using almost always the negative feedback. (We can not take advantage of the negative sign, because the sign of the relative errors is random.) Speaking of negative or positive feedback is only justified if A and ß are real quantities. Generally they are complex quantities, and the type of the feedback is a function of the frequency: E.g.
    [Show full text]
  • MT-033: Voltage Feedback Op Amp Gain and Bandwidth
    MT-033 TUTORIAL Voltage Feedback Op Amp Gain and Bandwidth INTRODUCTION This tutorial examines the common ways to specify op amp gain and bandwidth. It should be noted that this discussion applies to voltage feedback (VFB) op amps—current feedback (CFB) op amps are discussed in a later tutorial (MT-034). OPEN-LOOP GAIN Unlike the ideal op amp, a practical op amp has a finite gain. The open-loop dc gain (usually referred to as AVOL) is the gain of the amplifier without the feedback loop being closed, hence the name “open-loop.” For a precision op amp this gain can be vary high, on the order of 160 dB (100 million) or more. This gain is flat from dc to what is referred to as the dominant pole corner frequency. From there the gain falls off at 6 dB/octave (20 dB/decade). An octave is a doubling in frequency and a decade is ×10 in frequency). If the op amp has a single pole, the open-loop gain will continue to fall at this rate as shown in Figure 1A. A practical op amp will have more than one pole as shown in Figure 1B. The second pole will double the rate at which the open- loop gain falls to 12 dB/octave (40 dB/decade). If the open-loop gain has dropped below 0 dB (unity gain) before it reaches the frequency of the second pole, the op amp will be unconditionally stable at any gain. This will be typically referred to as unity gain stable on the data sheet.
    [Show full text]
  • Operational Amplifiers: Part 3 Non-Ideal Behavior of Feedback
    Operational Amplifiers: Part 3 Non-ideal Behavior of Feedback Amplifiers AC Errors and Stability by Tim J. Sobering Analog Design Engineer & Op Amp Addict Copyright 2014 Tim J. Sobering Finite Open-Loop Gain and Small-signal analysis Define VA as the voltage between the Op Amp input terminals Use KCL 0 V_OUT = Av x Va + + Va OUT V_OUT - Note the - Av “Loop Gain” – Avβ β V_IN Rg Rf Copyright 2014 Tim J. Sobering Liberally apply algebra… 0 0 1 1 1 1 1 1 1 1 Copyright 2014 Tim J. Sobering Get lost in the algebra… 1 1 1 1 1 1 1 Copyright 2014 Tim J. Sobering More algebra… Recall β is the Feedback Factor and define α 1 1 1 1 1 Copyright 2014 Tim J. Sobering You can apply the exact same analysis to the Non-inverting amplifier Lots of steps and algebra and hand waving yields… 1 This is very similar to the Inverting amplifier configuration 1 Note that if Av → ∞, converges to 1/β and –α /β –Rf /Rg If we can apply a little more algebra we can make this converge on a single, more informative, solution Copyright 2014 Tim J. Sobering You can apply the exact same analysis to the Non-inverting amplifier Non-inverting configuration Inverting Configuration 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 Copyright 2014 Tim J. Sobering Inverting and Non-Inverting Amplifiers “seem” to act the same way Magically, we again obtain the ideal gain times an error term If Av → ∞ we obtain the ideal gain 1 1 1 Avβ is called the Loop Gain and determines stability If Avβ –1 1180° the error term goes to infinity and you have an oscillator – this is the “Nyquist Criterion” for oscillation Gain error is obtained from the loop gain 1 For < 1% gain error, 40 dB 1 (2 decades in bandwidth!) 1 Copyright 2014 Tim J.
    [Show full text]