NETWORKED SYSTEM OF CRYSTAL OSCILLATORS
A Thesis
Presented to the
Faculty of
San Diego State University
In Partial Fulfillment
of the Requirements for the Degree
Master of Science in Applied Mathematics
with a Concentration in
Dynamical Systems
by
Steven Isaac Reeves
Spring 2016
iii
Copyright c 2016 by Steven Isaac Reeves iv
In solving a problem of this sort, the grand thing is to be able to reason backward.
– Sherlock Holmes v
ABSTRACT OF THE THESIS
NETWORKED SYSTEM OF CRYSTAL OSCILLATORS by Steven Isaac Reeves Master of Science in Applied Mathematics with a Concentration in Dynamical Systems San Diego State University, 2016
The dynamics of a system of coupled crystal oscillators (CCOST) is examined with the aim of developing a stable precision timing device. Symmetry is used to establish the existence and stability of collective patterns of oscillations in the CCOST device. We investigate N identical crystal oscillators, where each is described by a two-mode nonlinear oscillator circuit that exhibits SO(2) × SO(2)-symmetry. The coupling is assumed to be identical, and two different topologies, unidirectional and bidirectional, are considered. The unidirectional topology leads to a network with SO(2) × SO(2) × ZN -symmetry. On the other hand, the bidirectional topology yields a network with SO(2) × SO(2) × DN -symmetry. The possible patterns of oscillation are classified using these symmetries and their respective isotropy subgroups. The effects of noise on the unidirectional CCOST device will be investigated with respect to phase error reduction. Phase error reduction of certain patterns will be tested against an uncoupled-averaged control group. This work will instruct on the design rules for the proposed precision timing device. vi
TABLE OF CONTENTS PAGE ABSTRACT ...... v LIST OF TABLES...... vii LIST OF FIGURES ...... viii ACKNOWLEDGMENTS ...... xi CHAPTER 1 Introduction ...... 1 2 Crystal Oscillators ...... 4 2.1 Two-Mode Oscillator Model ...... 5 2.2 Averaging ...... 6 2.3 Stability ...... 8 3 Coupled Crystal Oscillator System...... 12 3.1 Averaged Equations ...... 12 3.2 Symmetries of Collective Patterns ...... 16 3.2.1 The unidirectional case ...... 17 3.2.2 The bidirectional case ...... 21 3.3 Isotypic Decomposition...... 28 3.4 Spectrum of Eigenvalues and Linear Stability ...... 31 4 Numerical Continuation ...... 38 4.1 Unidirectionally Coupled Ring ...... 38 4.2 Bidirectionally Coupled Ring ...... 44 5 Phase Error ...... 48 5.1 Uncoupled Control Group ...... 50 5.2 Unidirectional Coupling ...... 51 6 Discussion and Future Work...... 54 BIBLIOGRAPHY ...... 57 APPENDICES A Averaging...... 60 vii
LIST OF TABLES PAGE 2.1 Classification of solutions of Eq. (2.6) based on isotropy subgroups...... 9 3.1 One-dimensional irreducible representations and spatial subgroups of the bifurcating periodic solutions...... 22
3.2 Isotropy subgroups of periodic solutions bifurcating from DN Hopf bi- furcation at a Γ-simple subspace consisting of the sum of isomorphic two-dimensional absolutely irreducible representations of DN ...... 23 3.3 Spatial subgroups of the rotating waves bifurcating simultaneously from the symmetric Hopf bifurcation point...... 24 0 3.4 Possible spatial subgroups K depending on which element of K fixes the kernel (dg)(0,λ)...... 27 viii
LIST OF FIGURES PAGE 2.1 (Left) Schematic of a quartz crystal. (Right) A quartz crystal behaves like circuit composed of an inductor, capacitor and resistor, so it oscillates with a precise resonant frequency when it is subjected to an electric field...... 4 2.2 Two-mode crystal oscillator circuit. A second set of spurious RLC components (R2,L2,C2) are introduced by parasitic elements. [37] [33] ...... 5 2.3 Time series solutions of a single two-mode crystal oscillator model (2.4). (Top left) Two parameter bifurcation diagram indicating the regions of exis- tence of the time-series solutions as a function of parameters R1/a and R2/a. (Top right) Unstable Mixed Mode (i1(t), i2(t)), (bottom left) Stable Mode 1 (i1(t), 0) , (bottom right) Stable Mode 2 (0, i2(t)). Parameter values are: −4 −4 R1 = 30.9Ω, R2 = 181.1Ω, L1 = 5.2 × 10 H, L2 = 2.6 × 10 H, −13 −14 8 C1 = 1.0 × 10 F , C2 = 2.5 × 10 F , a = 939, b = 3 × 10 ...... 11 3.1 CCOST concept with unidirectionally coupled crystal oscillators...... 12 3.2 Rings of N = 16 oscillator units representing a 2π periodic so- 8 lution with spatial subgroups K = D2(κ, (π, γ )) (left) and K = 4 D2(κ, (π, γ )) (right) corresponding respectively to the cases m = 1 and m = 2. The various colors represent different waveforms and the numeric labels the relative phases between cells of same color, with 02 meaning oscillation at twice the frequency of the other units...... 26 3.3 Rings of N = 16 units representing a 2π-periodic solution with spatial 0 8 0 4 subgroups K = Z2(π, γ ) (left) and K = Z2(π, κγ ) (right) corre- sponding to the cases m = 1 and m = 2 respectively. The various colors represent different waveforms and the numeric labels the relative phases between cells of same color. Phase shifts between different col- ors are uncorrelated and 02 means oscillation at twice the frequency of the other units...... 29 4.1 Bifurcation diagrams for a ring of N = 3 crystal oscillators coupled unidi- rectionally in a ring configuration. The ring exhibits Z3-symmetry, i.e., cyclic permutations of three crystal oscillators. Parameter values are: R1 = 30.9Ω, −4 −4 −13 R2 = 181.1Ω, L1 = 5.2 × 10 H, L2 = 2.6 × 10 H, C1 = 1.0 × 10 F , −14 C2 = 2.5 × 10 F , a = 939, b = 3E08...... 39 4.2 Bifurcation diagrams for a ring of N = 4 crystal oscillators coupled unidi- rectionally in a ring configuration. The ring exhibits Z4-symmetry, i.e., cyclic permutations of four crystal oscillators. Parameter values: same as in Fig. 4.1 ...... 41 ix
4.3 Bifurcation diagrams for a ring of N = 5 crystal oscillators coupled unidi- rectionally in a ring configuration. The ring exhibits Z5-symmetry, i.e., cyclic permutations of five crystal oscillators. Parameter values: same as in Fig. 4.1 ...... 42 4.4 Bifurcation diagrams for a ring of N = 6 crystal oscillators coupled unidi- rectionally in a ring configuration. The ring exhibits Z6-symmetry, i.e., cyclic permutations of six crystals. Parameter values: same as in Fig. 4.1...... 44 4.5 Bifurcation diagrams for a ring of N crystal oscillators coupled biidirection- ally in a ring configuration. The diagrams depict the existence and stability of various branches of collective oscillations that appear, mainly via Hopf bifur- cations, as a function of coupling strength λ. The ring exhibits DN -symmetry, i.e., cyclic permutations of three crystal oscillators. Parameter values are: −4 −4 R1 = 30.9Ω, R2 = 181.1Ω, L1 = 5.2 × 10 H, L2 = 2.6 × 10 H, −13 −14 8 C1 = 1.0 × 10 F , C2 = 2.5 × 10 F , a = 939, b = 3 × 10 ...... 45 4.6 Two-parameter bifurcation diagrams for a ring of N crystal oscillators coupled biidirectionally in a ring configuration. Parameter values are: R1 = 30.9Ω, −4 −4 −13 R2 = 181.1Ω, L1 = 5.2 × 10 H, L2 = 2.6 × 10 H, C1 = 1.0 × 10 F , −14 8 C2 = 2.5 × 10 F , a = 939, b = 3 × 10 ...... 47 1 5.1 This figure displays 22MHz rotating wave solution, RW1 , of the unidirectional CCOST model, with 3 nodes and coupling strength λ = 0.99. Above, the −7 current, Xi, is plotted over a period of 1.0 × 10 seconds. Below, one noise function is displayed over the same duration...... 49 5.2 The uncoupled-averaged (λ = 0) phase error as a function of array size. The top section displays the average,√ maximum, and minimum phase errors of 50 samples for each N.A 1/ N scaling is observed. Below, the range of phase error values are displayed as a function of N. As N increases, we also see a general reduction in the sample range...... 50 5.3 The phase error with respect to the Synchronized Pattern with λ = −0.99 as a function of N. The top section of the figure displays the mean, maximum, and minimum√ phase errors for a 50 sample data set for each N. The average data fits a 1/ N reduction curve. Below, the range of possible values in the sample is shown. For most N, the range is decreasing, with notable exceptions of N = 7 and N = 10...... 52
5.4 The phase errors for the RW1 pattern as a function of the number of oscillators in the CCOST device when λ = 0.99. Above, the average, maximum and minimum phase errors of a sample of 50 simulations for each N is plotted. Additionally, the average data values fit a 1/N scaling. Below, the range of values is displayed as a function of N. The range decreases monotonically, illustrating the strength of this pattern...... 52 x
5.5 The phase errors with respect to the RW2 pattern as a function of N with λ = 0.99. The top section illustrates the average, maximum, and minimum phase errors of a 50 sample collection for each N. The data does not present a reduction for these values of N. Below, the range of values is represented as a function of N. While we do see a reduction in range, when N > 6 the mean values do not follow this trend...... 53 xi
ACKNOWLEDGMENTS I am incredibly thankful for my thesis committee chair and advisor, Dr. Antonio Palacios, for helping me in becoming a better researcher and mathematician. In addition, I am grateful for my thesis committee members, Dr. Peter Blomgren and Dr. Satish Sharma, without their support this thesis would not have been possible. Much of the calculations and support for this work is from the Office of Naval Research, and SPAWAR Systems Center Pacific. I thank the Office of Naval Research for funding for me and this work. I owe much to SPAWAR Systems Center Pacific and I thank Dr. Patrick Longhini and Dr. Visirath In in particular for their guidance and contributions to this work. I recognize the engineers at SPAWAR for their contribution to the experimental side of this project. I further acknowledge Dr. Ricardo Carretero and the Nonlinear Dynamical Systems group at San Diego State for giving me the tools to tackle a problem of this sort. 1
CHAPTER 1
INTRODUCTION
Precise time is crucial to a variety of economic activities around the world. Communication systems, electrical power grids, and financial networks all rely on precision timing for synchronization and operational efficiency. The free availability of GPS [2] time has enabled cost savings for industrial and scientific developments that depend on precise time and has led to significant advances in capability. For example, wireless telephone and data networks use GPS time to keep all of their base stations in synchronization. This allows mobile handsets to share limited radio spectrum more efficiently. Similarly, digital broadcast radio services use GPS time to ensure that the signals from all radio stations arrive at receivers in lockstep, so that listeners can tune between stations with minimum delay. However, even the most sophisticated satellite navigation equipment cannot operate in every environment. And even under perfect weather and environmental conditions, mechanical failure can still occur and hinder accessibility. In fact, many of the 32 satellites in the GPS constellation are operating past their intended lifespan or suffering from equipment failure. There have been a few launch incidents in past years, and the Air Force, which maintains the 30-year-old network, is overburdened with competing space priorities. Thus it is reasonable to wonder what would happen if the U.S. Global Positioning System is not available due to environmental or to complete mechanical failure. Regardless of the causes we could predict that if GPS were to fail completely, the cost would be severe. Civil aviation, trucking, shipping, and telecommunications would be rendered stationary, and countless other industries would be affected. Internet activity would slow to a crawl, because many internet service providers rely on precise GPS time stamps to route data. Agribusiness and commercial fishing could be blinded, causing food prices to skyrocket. For these reasons, GPS modernization has now become an ongoing initiative of the U.S. Government with new capabilities to meet growing military, civil and commercial needs [19]. Nevertheless, GPS service can degrade quickly when the signal is denied, impaired or otherwise unavailable. This thesis studies the possibility of developing a compact, high-precision, timing system using a Coupled Crystal Oscillator System or CCOST for short. The aim is to study the collective response of N crystal oscillators, coupled in some fashion, with the goal of creating robust stable oscillations to achieve high precision timing. Further, this work will provide a complete classification of the various patterns of collective behavior that are 2 created, mainly, through symmetry-breaking bifurcations, as well as the regions of existence and stability of each pattern, and finally examine the phase error reduction of a coupled system compared to the uncoupled standard. The results from this study will aid future simulations, design and fabrication tasks. Historically, the inability to determine longitude accurately made navigation on the open seas difficult and treacherous. In the Renaissance era, when Europe began its exploration, determining longitude required comparing the time at the current location with the time at a known location, say the Greenwich meridian. However, no shipboard clocks could determine time to an accuracy sufficient for navigational purposes. Heads of several seafaring nations offered great prizes for a solution to the problem of longitude. In the early 18th century, the Longitude Prize offered by Britain led to the development of the ship’s chronometer. [28] This device was so amazingly workable that it remained in use unchanged in its essential elements until the electronic era of the early 20th century. Following World War I and the development of the electronic oscillator and radio communications, the U.S. Navy took an ever more active role in the development of emerging Precision Time and Time Interval (PTTI) technologies. The U.S. Naval Observatory (USNO), the Naval Research Laboratory (NRL) and, after World War II, the Office of Naval Research (ONR), the Defense Advanced Research Projects Agency (DARPA) and the National Science Foundation [23] were important players in the development of the technology that makes up the current state of the art in PTTI [5]. The advances that had been made in high-frequency electronics during World War II radar research set the stage for the development of atomic clocks. In 1942 the Joint Chiefs of Staff established a Radio Propagation Laboratory at the National Bureau of Standards (NBS), now the National Institute of Standards and Technology (NIST). The Radio Propagation Laboratory developed the world’s first atomic clock in 1948. This clock was based on the measurement of a spectroscopic absorption line in ammonia. Because its stability was no better than that of high-quality quartz oscillators, the ammonia system was quickly abandoned for the greater potential accuracy of the cesium atomic beam device. At the heart of this device was a microwave cavity design developed in 1948 by Norman Ramsey of Harvard University (Ramsey received the Nobel Prize for this work in 1989.) Immediately following the launch of the first artificial Earth-orbiting satellite, Sputnik, by the Soviet Union in 1957, the Navy set up the Naval Space Surveillance System (NAVSPASUR). In 1964, Roger Easton of the NRL put forward a concept for an improved navigation system that would orbit precision clocks. Signals from such a satellite could provide more precise navigation as well as precise time signals that were available worldwide. To achieve this goal, NRL started programs to develop improved quartz frequency standards 3 suitable for spaceflight. Soon thereafter, the Timation program, which involved atomic clocks in space, was established. These space-qualified atomic clocks were then used in the Global Positioning System (GPS), GPS became a joint service program in 1973, with the Air Force designated executive agent for the system. Since 1976 the length of a second has been defined as the frequency of a specific resonant mode of the cesium atom. The frequency inaccuracy of the cesium clocks is approximately 8.64ns/day. In comparison the typical watch crystal has an error of about 20ppm, which is about 1.73s/day. The increased accuracy and precision comes with a price. Typical cost range of crystal oscillators are in the few dollars while a cesium clock can be in the order of $40,000. Currently, the accuracy of the NIST atomic clock, called NIST-F2 [27], is on the order of 1x10−16, making it on the order of three times as accurate as its predecessor NIST-F1, which had served as the standard since 1999. Both clocks use a ‘fountain’ of cesium atoms to determine a precise measure of a second. The key operational difference is that F1 operates near room temperature whereas the atoms in F2 are shielded within a much colder environment [16]. This thesis is organized as follows. The introduction provides an informative description for the general reader of the state-of-the-art in the development of precise timing devices, including, of course, atomic clocks. In Chapter 2 we introduce the physics behind crystal oscillators followed by a description of the equivalent electric circuit representation. A two-mode mathematical model of the circuit and its dynamic behavior is also presented in great detail. In Chapter 3 a comprehensive analysis of the collective response of a network of crystal oscillators is conducted. This network has two coupling topologies: a unidirectional topology and bidirectional topology forming ring structures. The former case leads to a system with ZN -symmetry, where ZN is the cyclic group of permutations of N objects. The latter case produces a system with DN -symmetry, where DN is the dihedral group of symmetries of an N-sided polygon. To classify the possible patterns of oscillations, we exploit the symmetry of the network to identify those patterns that can arise from local primary bifurcations at the equilibrium solution via equivariant Hopf bifurcations. We show that the periodic solutions are rotating waves, but with the phase shift patterns on the units in the ring having the structure of discrete rotating waves. Then, we study the existence of additional patterns that emerge via secondary bifurcations from rotating waves. In Chapter 4 computational bifurcation analysis of the collective response of a CCOST system with the aid of the continuation software package AUTO [11] is computed. Chapter 5 features the simulation of phase error of the unidirectional coupling topology against the uncoupled baseline. Lastly, this thesis concludes with a discussion on the results and research to come. 4
CHAPTER 2
CRYSTAL OSCILLATORS
A crystal is a solid in which the constituent atoms, molecules, or ions are packed in a regularly ordered, repeating pattern extending in all three spatial dimensions [30, 40]. Almost any object made of an elastic material could be used like a crystal, with the appropriate transducers, since all objects have natural resonant frequencies of vibration. For example, steel is very elastic and has a high speed of sound, so it was often used in mechanical filters before quartz. Resonant frequency depends on the size, shape, elasticity, and speed of sound within the material. High-frequency crystals are typically cut in the shape of a simple, rectangular plate. Low-frequency crystals, such as those used in digital watches, are typically cut in the shape of a tuning fork. For applications not needing very precise timing, a low-cost ceramic resonator is often used in place of a quartz crystal. When a crystal of quartz is properly cut and mounted, it can be made to distort in an electric field by applying a voltage to an electrode near or on the crystal. This property is known as electrostriction or inverse piezoelectricity. When the field is removed, the quartz will generate an electric field as it returns to its previous shape, and this can generate a voltage. The result is that a quartz crystal behaves like a circuit composed of an inductor, capacitor and resistor, with a precise resonant frequency [41], see Fig. 2.1.
Figure 2.1. (Left) Schematic of a quartz crystal. (Right) A quartz crystal behaves like circuit composed of an inductor, capacitor and resistor, so it oscillates with a precise resonant frequency when it is subjected to an electric field. 5 Quartz has the further advantage that its elastic constants and its size change in such a way that the frequency dependence on temperature can be very low. The specific characteristics will depend on the mode of vibration and the angle at which the quartz is cut (relative to its crystallographic axes). Therefore, the resonant frequency of the plate, which depends on its size, will not change much, either. This means that a quartz clock, filter or oscillator will remain accurate. For critical applications the quartz oscillator is mounted in a temperature-controlled container, called a crystal oven, and can also be mounted on shock absorbers to prevent external mechanical vibrations. Next we review the analysis of a single crystal oscillator model conducted in [22]. This presentation is motivated, however, from the group-theoretical and numerical perspectives.
2.1 TWO-MODE OSCILLATOR MODEL The crystal oscillator circuit sustains oscillation by applying a voltage signal from the quartz resonator, amplifying it, and feeding it back to the resonator. The rate of expansion and contraction of the quartz is the resonant frequency, and is determined by the cut and size of the crystal as mentioned in the previous paragraph. When the energy of the generated output frequencies matches the losses in the circuit, an oscillation can be sustained. The frequency of the crystal can be slightly adjusted by modifying the attached capacitances. A varactor, a diode with capacitance depending on applied voltage, is often used in voltage-controlled crystal oscillators, VCOs. The analog port of the VCO chip is modeled by a nonlinear resistor R−, see Fig. 2.2,
Figure 2.2. Two-mode crystal oscillator circuit. A second set of spurious RLC components (R2,L2,C2) are introduced by parasitic elements. [37] [33]
that obeys the voltage-current relationship
v = −ai + bi3, 6 where a and b are constant parameters. A major reason for the wide use of crystal oscillators is their high Q factor. This is a dimensionless parameter that indicates how under-damped an oscillator is. For a crystal oscillator, it can be defined as the ratio of the resonant frequency with respect to the half-power bandwidth, i.e., the bandwidth over which the power of vibration is greater than half the power at the resonant frequency. Higher Q indicates that the oscillations die out more slowly. A typical Q value for a quartz oscillator ranges from 104 to 106, compared to perhaps 102 for an LC oscillator. The inductance of the leads connecting the crystal to the VCO port is represented by
Lc. In addition, parasitic elements can be represented by a series resonator (L2, C2, R2) connected in parallel with the nonlinear resistor. The resulting circuit, depicted in Fig. 2.2, forms a two-mode resonator model. Applying Kirchhoff’s voltage law yields the following governing equations
2 d ij dij 1 2 di1 di2 Lj 2 + Rj + ij = [a − 3b(i1 + i2) ] + , (2.1) dt dt Cj dt dt where j = 1, 2 and Lc has been included in L1. Letting x1 = i1, x2 = di1/dt, x3 = i2 and 2 T x4 = di2/dt, ω0j = 1/LjCj and X = [x1, x2, x3, x4] , the model equations (2.1) can be rewritten as dX = F (X) ≡ AX + N (X), (2.2) dt where 0 1 0 0 0 0 a − R a −3b −ω2 1 0 (x + x )2(x + x ) 01 N1 1 3 2 4 L1 L1 L1 A = , N (X) = = . 0 0 0 1 0 0 a a − R −3b 2 2 N 2 0 −ω02 2 (x1 + x3) (x2 + x4) L2 L2 L2
The terms AX and N (X) represent the linear and nonlinear terms, respectively, which, together, govern the behavior of the two-mode crystal oscillator.
2.2 AVERAGING
In what follows we assume nonresonance conditions among ω01 and ω02, so that there ω p are no nonzero integers p and q for which 01 = . Using the Van der Pol transformation ω02 q 7
T U = Φ(t)X, where U = [u1, . . . , u4] and Φ(t) is the co-rotating frame of reference:
1 cos ω1t − sin ω1t 0 0 ω1 1 − sin ω1t − cos ω1t 0 0 Φ(t) = ω1 , 1 0 0 cos ω2t − sin ω2t ω2 1 0 0 − sin ω2t − cos ω2t ω2
Eq. (2.2) can be rewritten as
dU = εF (U, t), (2.3) dt where the derivatives are explicitely given by
1 u˙ = Ω u cos(ω t) − u sin(ω t) − N sin(ω t) 1 ω 1 1 1 2 1 1 1 1 1 v˙1 = Ω1 u1 cos(ω1t) − u2 sin(ω1t) − N1 cos(ω1t) ω1 1 u˙ = Ω u cos(ω t) − u sin(ω t) − N sin(ω t) 2 ω 2 3 2 4 2 2 2 2 1 v˙2 = Ω2 u3 cos(ω2t) − u4 sin(ω2t) − N2 cos(ω2t), ω2
2 2 2 2 with ω01 − ω1 = εΩ1 and ω02 − ω2 = εΩ2. Averaging over the periods T1 = 2π/ω1 and
T2 = 2π/ω2 we arrive at the simplified equation
dU = εF¯(U) ≡ εAU¯ + εN¯ (U), (2.4) dt
1 Z T where F¯(U) = lim F (U, t)dt and T →∞ T 0
a − R1 Ω1 − 0 0 u1 2 2 2 2 2L 2ω [u1 + u2 + 2(u3 + u4)] 1 1 L1 Ω a − R u 1 1 0 0 2 [u2 + u2 + 2(u2 + u2)] 3b 1 2 3 4 ¯ 2ω1 2L1 ¯ L1 A = , N (X) = − u . a − R2 Ω2 8 3 2 2 2 2 0 0 − [u3 + u4 + 2(u1 + u2)] 2L 2ω L2 2 2 u Ω a − R 4 2 2 2 2 2 2 [u3 + u4 + 2(u1 + u2)] 0 0 L2 2ω2 2L2
Equation (2.4) can be interpreted as a representation of the original model Eq. (2.2) with respect to two rotating frames of reference, one rotating with speed ω1 and one with 8
speed ω2. We invite the reader to see the appendix for the full averaging calculation. Observe
that in this rotating coordinate system, u1 = u2 = 0 and u3 = u4 = 0 are two invariant subspaces so that the two modes of oscillation of the crystal decouple from one another.
Using complex coordinates: z1 = u1 + u2 i and z2 = u3 + u4 i, and re-scaling time, the model Eq. (2.4) can be expressed as
3b 2 2 z˙1 = (µ1 + τ1i)z1 − (|z1| + 2|z2| )z1 8L1 3b 2 2 z˙2 = (µ2 + τ2i)z2 − (|z2| + 2|z1| )z2, 8L2
where µ1 = (a − R1)/(2L1), τ1 = Ω1/(2w1), µ2 = (a − R2)/(2L2) and τ2 = Ω2/(2w2). 1 1 −iτ1t −iτ2t Finally, letting z˜1 = √ z1e and z˜2 = √ z2e , we arrive, after dropping the˜marker, 8 8 at the following set of equations in complex coordinates:
3b z˙ = µ z − (|z |2 + 2|z |2)z 1 1 1 L 1 2 1 1 (2.5) 3b 2 2 z˙2 = µ2z1 − (|z2| + 2|z1| )z2. L2
Observe that in these coordinates, Eq. (2.5) commutes with a 2-Torus 2 4 2 T = SO(2) × SO(2), which acts on R = C diagonally by
iθ1 iθ2 (θ1, θ2) · (z1, z2) = (e z1, e z2),
2 2 where (θ1, θ2) ∈ T and (z1, z2) ∈ C .
2.3 STABILITY
The linearization of Eq. (2.5) about (z1, z2) = (0, 0) produces two pairs of complex eigenvalues a − R1 Ω1 σ1 = ± i 2L1 ω1 a − R2 Ω2 σ2 = ± i. 2L2 ω2
It follows that when both R1/a > 1 and R2/a > 1 the trivial equilibrium is asymptotically stable. In fact, we show below that in this region there it is the only solution so
U = (0, 0, 0, 0) is, actually, globally asymptotically stable. When R1/a < 1, while R2/a > 1 is fixed, the trivial solution loses stability and a limit cycle emerges, restricted to the invariant
subspace u3 = u4 = 0, via a standard Hopf bifurcation. This solution is called Mode 1
in [22]. Since u3 = u4 = 0 is invariant, it corresponds to only one current in the crystal 9 oscillating while the other remains zero, i.e., of the form (i1(t), 0). A similar scenario leads to
Mode 2 ,(0, i2(t)), along the invariant subspace u1 = u2 = 0, when R2/a < 1 while R1/a > 1 is now held fixed. In order to get a more complete picture of the regions of existence and stability of these modes of oscillations, we convert Eq. (2.4) to polar coordinates through the 2 2 3 4 transformation: ρ1 = u1 + u2 and ρ2 = u1 + u2. We get
(a − R ) 3b ρ˙ = 1 ρ − ρ ρ2 + 2ρ2 1 2L 1 8L 1 1 2 1 1 (2.6) (a − R2) 3b 2 2 ρ˙2 = ρ2 − ρ2 ρ2 + 2ρ1 . 2L2 8L2
The phase equations decouple from the amplitude equations due to the nonresonance conditions, thus they are not included in (2.6). It is important to note that now the amplitude equations (2.6) commute only with the standard action of the Z2 × Z2 symmetry group in the plane [14], which is what remains of the 2-torus T2 phase-shift symmetries. This type of reflectional symmetry commonly appears in engineering applications of nonlinear oscillators. In particular, it is found in classical systems such as: the pendulum equations [42], Duffing oscillators [18, 32] and Van der Pol oscillators [4, 9, 17, 35, 36]. In recent works, the same type of odd symmetry has appeared in modern systems that include: vibratory gyroscopes [3, 8, 34, 39, 38] and energy harvesting systems [6, 7, 24]. Equilibria of
Isotropy Solution Type
Z2 × Z2 (ρ1, ρ2) = (0, 0) Trivial Steady State r ! 4(a − R ) (1, −1) (ρ , ρ ) = 1 , 0 Mode 1: Periodic solution, period T = 2π/ω Z2 1 2 3b 01 r ! 4(a − R ) (−1, 1) (ρ , ρ ) = 0, 2 Mode 2: Periodic solution, period T = 2π/ω Z2 1 2 3b 02 ∗ ∗ 1 (ρ1, ρ2) = (ρ1, ρ2) Mixed-Mode: Invariant 2-torus Table 2.1. Classification of solutions of Eq. (2.6) based on isotropy subgroups. equations (2.6) correspond to steady states, limit cycles,and invariant two-tori in the original model Eq. (2.3). Specifically, there are four types of solutions and they can be classified based on their isotropy subgroups of Z2 × Z2, shown in Table 2.1. Modes 1 and 2 exist only if
R1/a < 1 and R2/a < 1, respectively. As indicated above, these periodic solutions appear as primary bifurcations off the trivial steady state via standard Hopf bifurcations. The bifurcation of either branch could be supercritical or subcritical depending on how the parameters R1/a 10 and R2/a are varied. For instance, if R2/a > 1 is held fixed while R1/a decreases below 1 then Mode 1 appears via a supercritical Hopf bifurcation as the trivial solution loses stability.
If we then follow the unstable branch of the trivial solution while decreasing R2/a a
subcritical Hopf bifurcation leads to Mode 2 as R2/a crosses 1. A similar scenario leads to a
supercritical Hopf bifurcation for Mode 2 followed by a subcritical one for Mode 1 as R1/a is
varied first and then R2/a. ∗ ∗ The mixed-mode solution (ρ1, ρ2) exists only inside the region (R1/a, R2/a) bounded
by R1/a < R2/(2a) + 1/2 < 1 and R2/a < R1/(2a) + 1/2 < 1. This is a two-frequency solution that lies on an invariant 2-torus. This 2-torus appears through a secondary bifurcation from the two pure modes. Generically, this family of 2-tori is either always stable or always unstable. For our model of crystal oscillators it is the latter case since the linearization of ∗ ∗ Eq. (2.6) about (ρ1, ρ2) yields positive real parts of eigenvalues. In this same region, the real parts of the eigenvalues of the linearization of Eq. (2.6) about Mode 1 and Mode 2 are both negative, leading to bistability between Modes 1 and 2. The time-series solutions and corresponding phase spaces for each individual pure mode and mixed-mode oscillation are shown in Fig. 2.3. The regions of existence and stability are depicted in the two-parameter bifurcation diagram also included in Fig. 2.3. In summary, Modes 1 and 2 can be stable. Bistability among these two modes is found in the region bounded by
R1/a < R2/(2a) + 1/2 < 1 and R2/a < R1/(2a) + 1/2 < 1, which is also the same region where the stable mixed-mode solution exists and is always unstable. The common point
where R1/a = R2/a = 1 corresponds to a codimension-two torus bifurcation at which two pairs of eigenvalues of the linearization of Eq. (2.2) about the trivial solution cross the
imaginary axis, i.e., a Hopf-Hopf bifurcation. The boundary curves R1/a = R2/(2a) + 1/2
and R2/a = R1/(2a) + 1/2, which are the locus of the secondary bifurcations that lead to a change of stability for Modes 1 and 2, respectively, meet at the torus bifurcation point. The presence of the two-frequency oscillations in the mixed mode is shown in the time-series plot shown in Fig. 2.3. A 3D phase-space visualization of the associated torus is also shown in Fig. 2.3. However, we emphasize that this mixed-mode solution is always unstable so it does not appear after transient integration. 11
(0,i ) (0,0) 1 2 (0,i ) x 10−3 0.8 2 2 1
/a 0.6
3 0 1 x
R −1 0.4 (i ,0) 1 −2 2 0.2 (i ,i ) (i ,0) 1 2 1 1 1 0.5 5 0 x 10 0 0 −1 −3 0 0.2 0.4 0.6 0.8 1 −0.5 x 10 −2 x −1 R /a 2 x 2 1 x 10−3
2 x x 1 1 x 0.01 x 3 3 1
0 0
−0.01 −1
−2 −0.02 400 500 600 700 800 800 820 840 860 880 t t
Figure 2.3. Time series solutions of a single two-mode crystal oscillator model (2.4). (Top left) Two parameter bifurcation diagram indicating the regions of existence of the time-series solu- tions as a function of parameters R1/a and R2/a. (Top right) Unstable Mixed Mode (i1(t), i2(t)), (bottom left) Stable Mode 1 (i1(t), 0) , (bottom right) Stable Mode 2 (0, i2(t)). Parameter values −4 −4 −13 are: R1 = 30.9Ω, R2 = 181.1Ω, L1 = 5.2 × 10 H, L2 = 2.6 × 10 H, C1 = 1.0 × 10 F , −14 8 C2 = 2.5 × 10 F , a = 939, b = 3 × 10 . 12
CHAPTER 3
COUPLED CRYSTAL OSCILLATOR SYSTEM
This chapter studies the collective behavior of a Coupled Crystal Oscillator System (CCOST) made up of N ∈ N, assumed to be identical, crystal oscillators. We consider first the case of unidirectional coupling in a ring fashion, as is shown schematically in Fig. 3.1.
The spatial symmetry of the ring is described by the group ZN of cyclic permutations of N objects. Since the dynamics of each node is still described by Eq. (2.5) with internal symmetry SO(2) × SO(2) then, effectively, the entire network symmetry is given by the group
Γunidir = SO(2) × SO(2) × ZN .
In the case of bidirectional coupling, the spatial symmetry is captured by the dihedral group DN of permutations of an N-gon, so the network symmetry is the group
Γbidir = SO(2) × SO(2) × DN .
In both cases, unidirectional and bidirectional coupling, we analyze the collective behavior of the network for arbitrary ring size N using classification of periodic solutions via their symmetry groups. Moreover, by using the isotypic decomposition of the phase space under the action of the group of symmetries we can study the linearized system of equations and calculate analytical expressions for the critical eigenvalues that lead to a wide range of symmetry-breaking bifurcations to patterns of collective behavior.
f2 f1
f3 fN
f4 f5
Figure 3.1. CCOST concept with unidirectionally coupled crystal oscillators. 13
3.1 AVERAGED EQUATIONS Applying Kirchhoff’s law to the CCOST network with unidirectional coupling yields the following governing equations
d2i di 1 L k,j + R k,j + i = a − 3b i + i − λi + i 2 k,j dt2 k,j dt C k,j k,1 k,2 k+1,1 k+1,2 k,j (3.1) di di di di k,1 + k,2 − λ k+1,1 + k+1,2 , dt dt dt dt
where k = 1, 2,...,N, j = 1, 2. Since we assume identical components in each crystal
oscillator, then the set of parameters reduces to: Lk,1 = L1, Lk,2 = L2, Rk,1 = R1, Rk,2 = R2,
Ck,1 = C1 and Ck,2 = C2. Eq. (3.1) can be rewritten in matrix form as follows
dX k = F (X ) − λB X + N (X ,X ), (3.2) dt k k+1 k k+1
0 0 T T where Xk = [ik1, ik1, ik2, ik2] = [xk1, . . . , xk4] , F (Xk) is the internal dynamics of each individual crystal as is described by Eq. (2.2). B is the matrix for the linear coupling terms while the vector N contains nonlinear coupling terms, they are given by
0 0 0 0 0 a a 3b os os 2 es es os es 0 0 − [(xk − λxk+1) (xk − λxk+1) − xk xk ] L1 L1 L1 B = , N (X) = , 0 0 0 0 0 a a 0 0 −3b os os 2 es es os es L L [(xk − λxk+1) (xk − λxk+1) − xk xk ] 2 2 L2
os es where xk = xk1 + xk3 and xk = xk2 + xk4. Using a similar set of Van der Pol
transformations and after averaging over the periods T1 = 2π/ω1 and T2 = 2π/ω2 we get the following set of equations:
dU k = εAU¯ − ελBU¯ + εN¯ (U ,U ), (3.3) dt k k+1 k k+1 14
T ¯ where Uk = [uk1, . . . , uk4] , A is the same matrix associated with the linear components of a single crystal oscillator, see Eq. (2.4), and a 0 0 0 2L N1 1 a 0 0 0 N2 ¯ 2L1 ¯ B = a , N (U) = , 0 0 0 N3 2L2 a 0 0 0 N4 2L2
where N1,..., N4 contain nonlinear terms in Uk and Uk+1. The actual expressions are too long to be listed here, however, the full averaging is included in the second portion of the
appendix. Complexifying again: zk1 = uk1 + uk2i and zk2 = uk3 + uk4i, we arrive at the network equations for a unidirectionally coupled CCOST system in the following form
3b 2 2 z˙k1 = (µk1 + iτk1)zk1 − ξ1zk+1,1 − |zk1| + 2|zk2| zk1+ 8L1 3bλ 2 2 (|zk1| + 2|zk2| )zk+1,1 + zk1z¯k+1,1 +z ¯k1zk+1,1 zk1 + 2 zk2z¯k+1,2 +z ¯k2zk+1,2 zk1 − 8L1 2 3bλ 2 2 |zk+1,1| + 2|zk+1,2| zk1 + zk1z¯k+1,1 +z ¯k1zk+1,1 zk+1,1 + 2 zk2z¯k+1,2 +z ¯k2zk+1,2 zk+1,1 8L1 3 3bλ 2 2 |zk+1,1| + 2|zk+1,2| zk+1,1 , 8L1