Geometry-constrained Degrees of Freedom Analysis for Imaging Systems: Monostatic and Multistatic
B. Mamandipoor(1), A. Arbabian(2) and U. Madhow(1)
(1) ECE Department, University of California, Santa Barbara, CA, USA (2) EE Department, Stanford University, Stanford, CA, USA Emails: {bmamandi, madhow}@ece.ucsb.edu, [email protected]
Abstract—In this paper, we develop a theoretical framework multistatic array presents difficulties in terms of both cost and for analyzing the measurable information content of an unknown complexity. In this paper, we consider two canonical active scene through an active electromagnetic imaging array. We imaging array architectures, monostatic and multistatic [8]. consider monostatic and multistatic array architectures in a one- dimensional setting. Our main results include the following: (a) A monostatic array consists of standalone transceiver (TRx) we introduce the space-bandwidth product (SBP), and show that, elements, i.e., when one of the elements is transmitting, only under the Born approximation, it provides an accurate prediction the co-located receiver collects the back-scattered signal. On of the number of the degrees of freedom (DoF) as constrained the other hand in a multistatic architecture, for any transmitting by the geometry of the scene and the imaging system; (b) we element, all of the receivers across the array collect the back- show that both monostatic and multistatic architectures have the same number of DoF; (c) we show that prior DoF analysis based scattered signal. In order to implement a multistatic array, on the more restrictive Fresnel approximation are obtained by we need to synchronize all of the TRx elements across the specializing our results; (d) we investigate matched-filter (back- aperture. For imaging at high carrier frequencies (e.g., using propagation) and pseudoinverse image reconstruction schemes, millimeter wave and THz bands), which offer the potential for and analyze the achievable resolution through these methods. Our significantly improved resolution, synchronization across large analytical framework opens up new avenues to investigate signal processing techniques that aim to reconstruct the reflectivity baselines is challenging, so that implementing a multistatic function of the scene by solving an inverse scattering problem, array presents significant difficulties in terms of both cost and and provides insights on achievable resolution. For example, we complexity. On the other hand, it is known that a multistatic show that matched-filter reconstruction leads to a significant architecture is capable of measuring a greater portion of the resolution loss for multistatic architectures. k-space spectrum for any point scatterer in the scene. It is therefore of significant interest to understand, at a fundamental I.INTRODUCTION level, potential improvements in information capacity (mea- The evaluation of the amount of information in an unknown sured in terms of DoF) that a multistatic architecture might be scene (object) that can be inferred through measurements able to provide. of radiated (or back-scattered) electromagnetic fields, is a We formulate the problem under the “Born approximation” fundamental problem that has relevance across different fields [9], which is based on a weak scattering model where the including optics [1], [2], wireless communications [3], [4], [5], total electromagnetic field at the scene is approximated by and electromagnetic imaging [6]. One of the crucial measures the incident field. Under this assumption, the measurement of the information capacity of such systems is the number of model is linearized, hence we can resort to singular value degrees of freedom (DoF). In general, a scene can be described decomposition (SVD) to analyze the model. Additionally, we by an infinite number of independent parameters. However, present a theory for DoF evaluation of narrowband (single the number of independent parameters that can be measured frequency) 1-dimensional (1D) monostatic and multistatic arXiv:submit/2353850 [cs.IT] 4 Aug 2018 through an imaging system is typically finite [7], and is given imaging systems, and provide guidelines for system design and by the number of DoF of the system. DoF analysis is of performance evaluation of image reconstruction techniques. both theoretical and practical significance: (i) it is related The ideas and results presented in this paper can be gener- to fundamental performance measures such as achievable alized to 2-dimensional (2D) and wideband (multi-frequency) resolution and the information capacity of the system, (ii) imaging systems. Detailed analysis for such settings is beyond it provides guidelines to design efficient and practical array the scope of the present paper. architectures under various cost and complexity constraints, A. Contributions (iii) it provides crucial insights on the performance of different image reconstruction algorithms. Our key contributions are as follows: While our focus here is on theoretical limits, we are 1) We introduce the space-bandwidth product (SBP), de- particularly interested in imaging at high carrier frequencies fined by the product of the scene area and the mea- (e.g., using millimeter wave bands), where synchronization surable Fourier extent of the scene as “seen” by the across large baselines is challenging, and implementing a imaging system (after removing redundancies), as an approximation to the DoF. SBP can be thought of as planes geometries. The authors in [2] present a general theory a generalization of the so-called Shannon number [10] for computing the electromagnetic DoF of optical systems for spectral measurements of an unknown scene through under arbitrary boundary conditions, following a sequential a space-variant bandlimited system. We evaluate the optimization framework for finding the strongest connected accuracy of our proposed DoF measure by comparing it source and receiving functions that span the input and output to numerical SVD computations for various geometries. spaces, respectively. This approach is equivalent to the SVD 2) We specialize our SBP analysis to deduce prior results of the system integral operator, and it shows that the number that had been derived for parallel planar surfaces using a of practically useful DoF are essentially finite under general more restrictive Fresnel approximation. We also provide boundary conditions. In this paper, we propose SBP as a a clear analysis of the design guidelines for multistatic measure to predict the number of DoF, and use numerical arrays that are based on the “effective aperture” concept. SVD computations to verify the accuracy of our measure for 3) We investigate image formation techniques that aim various geometries. to reconstruct the reflectivity function of the scene by The term space-bandwidth product has been previously used solving an inverse scattering problem. We show that in a somewhat different context, for evaluating the information the SVD analysis provides an easy understanding of content of optical signals and systems [23], [24]. In this the measurement process, as well as the achievable setting, it is defined as the area within the Wigner distribution resolution of various reconstruction schemes. In partic- representation of a signal. The latter forms an intermediate ular, we show that back-propagation reconstruction for signal description between the pure spatial representation and multitstaic architecture is highly suboptimal and leads the pure Fourier domain representation, and can be roughly to a significant loss in image resolution. interpreted as the local spatial spectrum of the signal [25]. The Wigner distribution has been derived for a 1D signal and B. Related Work its corresponding 1D Fourier Transform, and does not apply Classical theories for DoF analysis of imaging systems to our measurement model, where the desired information are based on the Shannon sampling theorem. In a series is seen through an active electromagnetic imaging system. of fundamental papers, Di Francia derived the significant In our definition of space-bandwidth product, the (spatial) conclusion that an image formed through a finite size aperture “bandwidth” is the k-space spectrum for each point scatterer in has a finite number of DoF [7], [11]. Since there is no the scene, which depends on the imaging system. This is then limitation on the number of DoF of the scene, it follows that integrated over all of the point scatterers constituting the scene, many different scenes can map to exactly the same image. or “space,” to obtain the space-bandwidth product. Thus, However, this result is not mathematically correct, as has space-bandwidth product as defined in this paper depends on been pointed out by multiple authors [12], [13]. The reason the geometry of both the imaging system and the scene. is that, if the scene is of finite size, then the knowledge of its Fourier transform over a bounded domain is enough to C. Organization reconstruct it exactly by using analytic continuation. In order Section II presents the measurement model and mathe- to account for the inevitable existence of noise in practical matical background for SVD analysis and the k-space rep- systems, it is necessary to introduce the notion of effective, resentation of the system. Sections III investigates the k- or practically useful, DoF [1]. This can be accomplished by space spectrum corresponding to a point scatterer seen through applying the seminal work of Slepian, Landau, and Pollak on monostatic and multistatic array architectures. In Section IV, prolate spheroidal wave functions (PSWFs) [14], [15]. The we go through the details of SBP computations for different PSWF theory shows that the eigenvalues corresponding to a imaging geometries, and verify the accuracy of the results finite Fourier integral operator are approximately constant up by numerical SVD computations. Section V investigates the to a critical point, after which they decay exponentially to zero. implications of the the Fresnel approximation for parallel Consequently, in the presence of noise, only a finite number planes geometry; it shows that SBP computations converge of eigenvalues can be used to accurately determine the output to approximate solutions of previous models, and provides in- of the integral operator. sights for the design of multistatic arrays in the Fresnel regime. The PSWF theory can be directly applied to the geometry In Section VI we investigate image formation techniques that of symmetric parallel planar surfaces in the far field, where aim to solve the inverse scattering problem, and analyze the we can use the Fresnel approximation [16], [17] for analyzing achievable resolution for monostatic and multistatic arrays. the measurement model [18], [19], [20]. It has been shown Finally, our conclusions are presented in Section VII. using this approach that the number of DoF of such imaging systems is also finite, and that the corresponding eigenfunc- II.MATHEMATICAL MODELAND BACKGROUND tions are related to the PSWFs. Similar techniques have been Consider the 1D aperture depicted in Figure 1. The scene applied to analyze multiple observation domains [21] and (object) is located at the origin, with the corresponding re- orthogonal planes geometry [22]. However, these results do flectivity function defined by γ : A → C, where A ⊂ R2 not directly generalize to short range (where the Fresnel is bounded. We restrict the Tx and Rx antenna elements to approximation is not accurate), or to asymmetric or tilted be located on the same plane: za = −D. Assume that the to the class of Hilbert-Schmidt operators, and is compact [27]. By virtue of linearity and compactness, we can invoke the Spectral Theorem [27], [28], and introduce the singular
value decomposition of Ξ, denoted by {σi, ψi, φi}i N, where + ∈ σi ∈ R are the singular values, and ψi ∈ Ψ and φi ∈ Φ are the right and left singular functions, respectively. The operator s = Ξγ can therefore be expressed as
X∞ s = σiφihγ, ψiiΨ, (5) i=1
where h·, ·iΨ denotes the inner product in Ψ. The SVD of Ξ is equivalent to the following series expansion of the integral Fig. 1. Geometry of 1-dimensional bistatic pair at distance za = −D from kernel in (2): the center of the scene. X∞ ξ(xtx, xrx, x0, z0) = σiφi(xtx, xrx)ψi∗(x0, z0). (6) i=1 Tx element located at (xtx, za) illuminates the entire scene, and that the Rx element located at , measures the (xrx, za) The sets of singular functions {ψi}i N and {φi}i N are back-scattered signal. The observed signal over an aperture orthonormal bases for Ψ and Φ, respectively.∈ From (5),∈ we of length L1 is denoted by s : B → C, where B = obtain the following one-to-one correspondence between the [−L1/2,L1/2] × [−L1/2,L1/2]. The relationship between two sets of singular functions, the scene reflectivity function and the observed signal over 1 the aperture is governed by the Helmholtz wave equation φi = Ξψi, ∀i. (7) σ [26]. Under the Born approximation [9], the solution of the i scalar Helmholtz equation for homogenous isotropic media A. Sum rule for computing the operator norm (simplified by dropping space attenuation factors) satisfies the Using Parseval’s Theorem, it is easy to see the following following linear integral equation: sum rule [2], [3] (see Appendix A for the proof), Z s γ (1) 2 X∞ 2 (xtx, xrx) = ξ(xtx, xrx, x0, z0) (x0, z0)dx0dz0, ||Ξ||HS = σi , (8) i=1 A where i.e., the square of the operator norm is equal to the sum of
0 0 0 0 strengths of its SVD components. Square integrability of the jkR(xtx,x ;z ) jkR(xrx,x ;z ) ξ(xtx, xrx, x0, z0) = e− e− , (2) kernel in Equation (4) leads to denotes the space-variant impulse response of the system, and X∞ 2 p 2 2 σ < ∞, (9) R(x, x0; z0) , (x − x0) + (za − z0) is the Euclidean dis- i i=1 tance between the point (x, za) on the aperture plane, and the point scatterer in the scene located at (x0, z0). The wavenumber that is, the sum of squares of the singular values of a Hilbert- 2π is denoted by k = λ , where λ is the signal wavelength. We Schmidt operator converges [27]. Therefore, putting the se- 2 2 assume γ ∈ Ψ and s ∈ Φ, where Ψ , L (A) and Φ , L (B) quence of singular values in non-increasing order, we have 2 represent the Hilbert spaces of square integrable functions over σi → 0 for i → ∞. In other words, although in principle the A and B, respectively. This assumption places the (physically number of nonzero singular values could be infinite, the num- plausible) restriction that the scene reflectivity function and ber of practically useful singular values is finite [1], [2]. The ¯ P the scattered electromagnetic fields have finite energy values. normalized sum of singular values Σ = i(σi/σmax) [10], It is convenient to recast the linear observation model in the [15], or the normalized sum of squares of the singular values ¯ 2 2 following operator form: Σsq = ||Ξ||HS/σmax [2], where σmax = σ1 = max{σi}, can be associated with the number of degrees of freedom s = Ξγ, (3) for a system with a steplike behavior of the singular values where Ξ:Ψ → Φ is defined by the right-hand side of (1). It , where all useful nonzero singular values are approximately is easy to see that the integral kernel (2) satisfies equal up to a certain threshold, after which they rapidly decay ¯ ZZ to zero. Note that for computing Σsq we can sidestep the SVD 2 2 ||Ξ||HS , |ξ(xtx, xrx, x0, z0)| dxtxdxrxdx0dz0 < ∞, computation by using (4) and only computing the maximum singular value of the operator. In general, this steplike behavior AB (4) is not satisfied for imaging systems, and the singular values where ||Ξ||HS denotes the Hilbert-Schmidt norm (extension decay gradually to zero [2]. A key goal in this paper is to find of Frobenius norm to possibly infinite dimensional Hilbert a simple criterion to determine the number of useful nonzero spaces) of the integral operator Ξ. Therefore, Ξ belongs singular values of Ξ for different imaging scenarios. Invariance of the operator norm to the relative geometry: points. Thus, an approximate solution for the 1D FTs in (13) The integral kernel in (2) has unit magnitude over its entire is given by parameter space. Therefore, the operator norm in (4) reduces 0 0 sp 0 0 sp jkR(xtx,x ;z ) jkR(xtx ,x ;z ) jkx xtx to, FT1D{e− } ≈ e− e− tx 0 0 sp 0 0 sp jkR(xrx,x ;z ) jkR(x ,x ;z ) jkx x 2 FT1D{e− } ≈ e− rx e− rx rx .(14) ||Ξ||HS = V V , (10) A B sp sp where V , V represent the volume of the sets A and B, where xtx and xrx are stationary points in the Fourier integral respectively.A ThisB observation indicates that for the measure- arguments, which are easily shown to satisfy ment model in (1), the operator norm as well as the dependent sp sp kxtx R(xtx, x0; z0) = k(x0 − xtx) criteria for estimating the degrees of freedom (e.g., Σ¯ sq), are k R(xsp , x ; z ) = k(x − xsp ). (15) invariant to the relative geometry of the aperture and the scene, xrx rx 0 0 0 rx and hence are not capable of capturing the effect of rotation We now utilize these expressions to reduce (14) into a function and translation of the scene (or the aperture) on the available of x0 and z0. In the process, we provide a geometric interpre- degrees of freedom of the imaging system. In general, the tation of the stationary phase approximation. number of independent parameters that we can extract from an Geometric interpretation of stationary phase approxima- unknown object using a linear operator is precisely determined tion: Consider a given point scatterer located at (x0, z0), by the number of nonzero singular values of the operator. and a given bistatic Tx/Rx pair, depicted in Figure 2-a. For our simulations we compute the singular system of the The stationary phase condition (15) simply characterizes the operator Ξ by discretizing the kernel provided by equation spatial frequency components corresponding to the dominant (2), over the parameter spaces A and B, and compute the propagating plane waves for this geometry. In particular, it can SVD numerically. In the next subsection, we review the k- be rewritten as space (spatial frequency domain) representation of the integral operation in Equation (1), which is a crucial step in defining kxtx = k sin(θtx), kxrx = k sin(θrx). (16) the SBP of the imaging system. Substituting this into the phase term for the first equation in B. k-space representation (14), we obtain sp sp Taking the 2D Fourier Transform (FT) of s(xtx, xrx) of the kR(xtx, x0; z0) + kxtx xtx received signal given by (1) and (2) over the aperture, yields = k(z0 − za)/ cos(θtx) + kxtx (x0 − (z0 − za) tan(θtx)) the data representation in the spatial frequency domain, = kxtx x0 + k cos(θtx)(z0 − za)
S(kxtx , kxrx ) = FT2D{s(xtx, xrx)} = kxtx x0 + kztx (z0 − za), (17) ZZ jkxtx xtx jkxrx xrx , s(xtx, xrx)e− e− dxtxdxrx.(11) where it becomes natural to define kztx = k cos(θtx) as the
xtxxrx dominant spatial frequency in the z direction for the Tx. An entirely similar computation and interpretation holds for the Substituting the expression for s(xtx, xrx) from (1), and second equation in (14). changing the order of integration yields To summarize, the stationary phase approximation corre- sponds to propagation along the dominant spatial frequencies S(kxtx , kxrx ) = ZZ along the x and z directions for the Tx and Rx, given in terms ˜ γ(x0, z0) ξ(kxtx , kxrx , x0, z0)dx0dz0, (12) of viewing angles shown in Figure 2-a as follows: z0x0 q 2 2 kxtx = k sin(θtx), kztx = k cos(θtx) = k − kx , ˜ tx where ξ(kxtx , kxrx , x0, z0) = FT2D{ξ(xtx, xrx, x0, z0)} de- q 2 − 2 notes the space-variant transfer function of the system. The kxrx = k sin(θrx), kzrx = k cos(θrx) = k kxrx . (18) 2D FT operator can be decomposed into two 1D Fourier We can now write the 1D Fourier transforms in (14) as Transforms as follows: 0 0 0 0 jkR(xtx,x ;z ) jkz (z za) jkx x FT1D{e− } ≈ e− tx − e− tx ξ˜(kx , kx , x0, z0) = tx rx jkR(x ,x0;z0) jk (z0 z ) jk x0 0 0 0 0 rx zrx a xrx jkR(xtx,x ;z ) jkR(xrx,x ;z ) FT1D{e− } ≈ e− − e− (19), FT1D{e− }FT1D{e− }, (13) Substituting (13) and (19) in (12) yields the following approx- where FT {f(α)} R f(α)e jkααdα. 1D , α − imation for the 2D spectrum: We now estimate the 1D FTs in (13) using the method of j(kztx +kzrx )za stationary phase [29], [30], which provides an approximate S(kxtx , kxrx ) ≈ e × solution for integrals of oscillatory functions. The method ZZ 0 0 j(kx +kxrx )x j(kz +kzrx )z involves determining the points where the phase is stationary γ(x0, z0)e− tx e− tx dx0dz0 (i.e., where the derivative equals zero), and replacing the z0x0 j(kztx +kzrx )za integral with the sum of the function values at the stationary = e γ˜(kxtx + kxrx , kztx + kzrx ), (20) i.e., the `2-norm of kγ is ||kγ ||2 = 2k, and its direction is determined by the corresponding viewing angle θtx = θrx. Figure 4-a shows the spectral content (corresponding to the point scatterer in Figure 3) seen through a monostatic array of infinitely many (co-located) Tx and Rx elements. We see that kγ lies on the arc of the circle of radius 2k, confined by the angles α and β, the two extremes of viewing angles from the aperture (also depicted in Figure 3). Consequently, the monostatic spectrum corresponding to a point scatterer is given by
(a) Tmono = {2ktx : ||ktx||2 = k, α ≤ ∠ktx ≤ β}. (22)
(b) Fig. 3. Geometry G1: 1D parallel and symmetric propagation model.
Fig. 2. (a) The geometry of bistatic Tx/Rx elements and a point scatterer in Monostatic Multistatic the scene, (b) the corresponding sampled point in the spectrum of the point 500 500 scatterer in k-space. 400 400 300 300 200 200 100 100
where γ˜(kx, kz) FT2D{γ(x0, z0)}, is the 2D spectrum of ) )
★ , 0 0 ★
/(2 /(2
✧ ✧
the scene reflectivity function. Let us define the 2D k-space x x k -100 k -100 vectors corresponding to the Tx and Rx as ktx = (kxtx , kztx ), -200 -200 and krx = (kx , kz ), respectively. From equation (20), we rx rx -300 -300 see that the spectrum of the scene has been sampled at -400 -400 -500 -500
kγ , (kx, kz) = ktx + krx 0 200 400 0 200 400 ✦ k /(2 ✦ ) k /(2 ) z z (a) (b) = (kxtx + kxrx , kztx + kzrx ), (21)
That is, kγ is the summation of two vectors ktx and krx, Fig. 4. k-space spectrum corresponding to point scatterer in Figure 3, seen each of which lie on the ring of radius k. Therefore, using through (a) monostatic and (b) multistatic array of infinitely many TRx elements. (21) and (18), we can characterize the k-space spectrum of a point scatterer for any given array architecture. For instance, On the other hand, in a multistatic array, the Tx and Rx Figure 2-b shows the sampled point (kγ ) in the spectrum of elements are not forced to be co-located, hence they can have the point scatterer in Figure 2-a. See [30], [16] for more details different viewing angles. Figure 4-b shows the spectral content on the k-space representation of active imaging systems. of the point scatterer seen through a multistatic array. For θtx =6 θrx, we have III. k-SPACE SPECTRUM FOR MONOSTATIC AND MULTISTATIC ARRAYS ||kγ ||2 = 2k cos(|θtx − θrx|/2) < 2k. (23) Consider the 1-dimensional array geometry depicted in Hence, the multistatic array not only samples the region of Figure 3. Let us restrict γ(x0, z0) to a plane parallel to the the spectrum seen by a monostatic array, but is also able to aperture with reflectivity γ(x0) , γ(x0, z0 = 0). Let L1, sample points that are inside the circle of radius 2k. Note that L2, and D denote the size of the aperture, the size of the the angular extent of the sampled region, determined by the scene, and the distance between the aperture and the scene, extreme viewing angles α and β, is the same for monostatic respectively. For any point scatterer located at x = x0 we and multistatic arrays. The multistatic spectrum corresponding can identify the spectral region that will be sampled using to a point scatterer is given by a specific array geometry. A monostatic architecture restricts the Tx and Rx to be co-located, hence, for any array element Tmulti = {ktx + krx : ||ktx||2 = ||krx||2 = k, we have ktx = krx. By equation (21), we have kγ = 2ktx, α ≤ ∠ktx ≤ β, α ≤ ∠krx ≤ β}. (24) It is easy to see that Tmulti can also be written as, for each position x0. Substituting γ(x0) = γ(x0, z0 = 0) in (20) gives
Tmulti = {(p1 + p2)/2 : p1, p2 ∈ Tmono}. (25) Z 0 j(kztx +kzrx )za j(kxtx +kxrx )x S(kxtx , kxrx ) = e γ(x0)e− dx0 Therefore, x0 Z 0 jkz za jkxx = e γ(x0)e− dx0. (27) Tmono ⊆ Tmulti ⊆ conv(Tmono), (26) x0 where conv(T ) denotes the convex hull of the set T . Note that the integral kernel in (27) only depends on kx =
Effective monostatic: As shown in Figure 2, a spatially- kxtx + kxrx . That is, any pair of Tx/Rx elements that leads separated pair of Tx/Rx elements samples the spectrum of a to the same spatial frequency in the x direction captures the point scatterer at kγ , where ||kγ || = 2k cos(|θtx−θrx|/2), and exact same information about the scene. Hence, in order to avoid redundancy in the acquired information, we consider ∠kγ = (θtx +θrx)/2. Therefore, for a given point scatterer in the scene, the same information can be captured by replacing the projection of the sampled points in the spectrum onto the Tx/Rx pair with a monostatic element located at xeff ∈ the kx axis. For any point scatterer located at x = x0, let spatial frequency bandwidth [xtx, xrx], such that θeff = (θtx + θrx)/2, and transmitting a us define the B(x0) as the width sinusoidal wave of wavelength λeff = λ/ cos(|θtx − θrx|/2). of the corresponding spectrum after the projection operation. Note that xeff , λeff , and the resulting effective monostatic Figure 5 shows B(x0) corresponding to the point scatterer in array depends on the viewing angles for a specific point Figure 3, for monostatic and multistatic array architectures. scatterer, and cannot be generalized to the entire scene. In The following theorem will be useful in characterizing the Section V, where we investigate the Fresnel approximation SBP of 1D imaging system.
(in the far field), we show that the dependence on scatterer Monostatic Multistatic location disappears in this regime, so that we can define an 500 500 400 400 effective monostatic array that applies to the entire scene. 300 300 Remark 1: The computation of the operator norm for the 200 200 P 2 100 100 1-dimensional array geometry leads to ∞ being equal ) )
σ B★ (x′) B(x′)