ECE-501 Phil Schniter February 4, 2008 replacements Complex-Baseband Equivalent Channel: Linear communication schemes (e.g., AM, QAM, VSB) can all be represented (using complex-baseband mod/demod) as: wideband modulation demodulation channel s(t) r(t) m˜ (t) Re h(t) + LPF v˜(t) × × j2πfct w(t) j2πfct ∼ e ∼ 2e− It turns out that this diagram can be greatly simplified. First, consider the signal path on its own: s(t) x(t) m˜ (t) Re h(t) LPF v˜s(t) × × j2πfct j2πfct ∼ e ∼ 2e− Since s(t) is a bandpass signal, we can replace the wideband channel response h(t) with its bandpass equivalent hbp(t): S(f) S(f) | | | | 2W f f ...because filtering H(f) Hbp(f) s(t) with h(t) is | | | | equivalent to 2W filtering s(t) f ⇔ f with hbp(t): X(f) S(f)H (f) | | | bp | f f 33 ECE-501 Phil Schniter February 4, 2008 Then, notice that j2πfct j2πfct s(t) h (t) 2e− = s(τ)h (t τ)dτ 2e− ∗ bp bp − · # ! " j2πfcτ j2πfc(t τ) = s(τ)2e− h (t τ)e− − dτ bp − # j2πfct j2πfct = s(t)2e− h (t)e− , ∗ bp which means we can rewrit!e the block di"agr!am as " s(t) j2πfct m˜ (t) Re hbp(t)e− LPF v˜s(t) × × j2πfct j2πfct ∼ e ∼ 2e− j2πfct We can now reverse the order of the LPF and hbp(t)e− (since both are LTI systems), giving s(t) j2πfct m˜ (t) Re LPF hbp(t)e− v˜s(t) × × j2πfct j2πfct ∼ e ∼ 2e− Since mod/demod is transparent (with synched oscillators), it can be removed, simplifying the block diagram to j2πfct m˜ (t) hbp(t)e− v˜s(t) 34 ECE-501 Phil Schniter February 4, 2008 Now, since m˜ (t) is bandlimited to W Hz, there is no need to j2πfct model the left component of Hbp(f + f ) = hbp(t)e− : c F{ } Hbp(f) Hbp(f + fc) H˜ (f) | | | | | | f f f fc fc 2fc 0 B 0 B − − − j2πfct Replacing hbp(t)e− with the complex-baseband response h˜(t) gives the “complex-baseband equivalent” signal path: m˜ (t) h˜(t) v˜s(t) The spectrums above show that h (t) = Re h˜(t) 2ej2πfct . bp { · } Next consider the noise path on it’s own: LPF(f) w(t) LPF v˜ (t) | | × n j2πfct f 2e Bs Bp W W Bp Bs ∼ − − − − From the diagram, v˜n(t) is a W (f) baseband version of the band- | | f f f pass noise spectrum that oc- − c c W (f + f ) cupies the frequency range | c | f [f B , f + B ]. f c s c s B B ∈ − − s s V˜n(f) Since v˜n(t) is complex-valued, | | ˜ f Vn(f) is non-symmetric. B B − s s 35 ECE-501 Phil Schniter February 4, 2008 Say that w(t) is real-valued white noise with power spectral density (PSD) Sw(f) = N0. Since Sw(f) is constant over all f, the PSD of the complex noise v˜n(t) will be constant over the LPF passband, i.e., f [ B , B ]: ∈ − p p Sv˜n (f) f B B W W B B − s − p − p s A well-designed communications receiver will suppress all energy outside the signal bandwidth W , since it is purely noise. Given that the noise spectrum outside f [ W, W ] ∈ − will get totally suppressed, it doesn’t matter how we model it! Thus, we choose to replace the lowpass complex noise v˜n(t) with something simpler to describe: white complex noise w˜(t) with PSD Sw˜(f) = N0: Sw˜(f) f B B W W B B − s − p − p s We’ll refer to w˜(t) as “complex baseband equivalent” noise. 36 ECE-501 Phil Schniter February 4, 2008 Putting the signal and noise paths together, we arrive at the complex baseband equivalent channel model: complex baseband equivalent channel ˜ j2πfct hbp(t) = Re h(t) 2e m˜ (t) h˜(t) + v˜(t) { · } w˜(t) = complex-valued white noise w˜(t) complex baseband bandpass equiv complex baseband modulation channel demodulation ⇔ s(t) r(t) m˜ (t) Re hbp(t) + LPF v˜(t) × × j2πfct w(t) j2πfct ∼ e ∼ 2e− I/Q modulation wideband I/Q demodulation ⇔ channel m (t) LPF v (t) I × × I cos(2πfct) s(t) r(t) cos(2πfct) + h(t) + ∼ ∼ sin(2πfct) sin(2πfct) − m (t) w(t) − LPF v (t) Q × × Q The diagrams above should convince you of the utility of the complex-baseband representation in simplifying the system model! 37.