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Signal Processing 86 (2006) 639–697 www.elsevier.com/locate/sigpro Review Cyclostationarity: Half a century of research
William A. Gardnera, Antonio Napolitanob,Ã, Luigi Paurac
aStatistical Signal Processing Incorporated (SSPI), 1909 Jefferson Street, Napa, CA 94559, USA bUniversita` di Napoli ‘‘Parthenope’’, Dipartimento per le Tecnologie, via Acton 38, I-80133 Napoli, Italy cUniversita` di Napoli ‘‘Federico II’’, Dipartimento di Ingegneria Elettronica e delle Telecomunicazioni, via Claudio 21, I-80125 Napoli, Italy
Received 22 December 2004; accepted 29 June 2005 Available online 6 September 2005
Abstract
In this paper, a concise survey of the literature on cyclostationarity is presented and includes an extensive bibliography. The literature in all languages, in which a substantial amount of research has been published, is included. Seminal contributions are identified as such. Citations are classified into 22 categories and listed in chronological order. Both stochastic and nonstochastic approaches for signal analysis are treated. In the former, which is the classical one, signals are modelled as realizations of stochastic processes. In the latter, signals are modelled as single functions of time and statistical functions are defined through infinite-time averages instead of ensemble averages. Applications of cyclostationarity in communications, signal processing, and many other research areas are considered. r 2005 Elsevier B.V. All rights reserved.
Keywords: Cyclostationarity; Almost-cyclostationary time series; Almost-cyclostationary processes; Bibliography
Contents
1. Introduction ...... 641 2. General treatments...... 642 3. General properties and structure of stochastic processes and time-series ...... 642 3.1. Introduction ...... 642 3.2. Stochastic processes ...... 643 3.2.1. Continuous-time processes ...... 643 3.2.2. Discrete-time processes ...... 645
ÃCorresponding author. Tel.: +39 081 768 37 81; fax: +39 081 768 31 49. E-mail addresses: [email protected] (W.A. Gardner), [email protected] (A. Napolitano), [email protected] (L. Paura).
0165-1684/$ - see front matter r 2005 Elsevier B.V. All rights reserved. doi:10.1016/j.sigpro.2005.06.016 ARTICLE IN PRESS
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3.3. Time series ...... 646 3.3.1. Continuous-time time series ...... 646 3.3.2. Discrete-time time series ...... 648 3.4. Link between the stochastic and fraction-of-time approaches ...... 649 3.5. Complex processes and time series ...... 649 3.6. Linear filtering ...... 650 3.6.1. Structure of linear almost-periodically time-variant systems ...... 650 3.6.2. Input/output relations in terms of cyclic statistics ...... 650 3.7. Product modulation ...... 651 3.8. Supports of cyclic spectra of band limited signals ...... 652 3.9. Sampling and aliasing...... 653 3.10. Representations by stationary components ...... 654 3.10.1. Continuous-time processes and time series ...... 654 3.10.2. Discrete-time processes and time series...... 655 4. Ergodic properties and measurement of characteristics ...... 656 4.1. Estimation of the cyclic autocorrelation function and the cyclic spectrum ...... 656 4.2. Two alternative approaches to the analysis of measurements on time series ...... 657 5. Manufactured signals: modelling and analysis ...... 658 5.1. General aspects ...... 658 5.2. Examples of communication signals...... 659 5.2.1. Double side-band amplitude-modulated signal ...... 659 5.2.2. Pulse-amplitude-modulated signal ...... 659 5.2.3. Direct-sequence spread-spectrum signal ...... 660 6. Natural signals: modelling and analysis ...... 661 7. Communications systems: analysis and design ...... 661 7.1. General aspects ...... 661 7.2. Cyclic Wiener filtering ...... 661 8. Synchronization...... 663 8.1. Spectral line generation...... 663 9. Signal parameter and waveform estimation ...... 663 10. Channel identification and equalization ...... 664 10.1. General aspects ...... 664 10.2. LTI-system identification with noisy-measurements ...... 664 10.3. Blind LTI-system identification and equalization...... 665 10.4. Nonlinear-system identification ...... 665 11. Signal detection and classification, and source separation ...... 665 12. Periodic AR and ARMA modelling and prediction...... 666 13. Higher-order statistics ...... 666 13.1. Introduction ...... 666 13.2. Higher-order cyclic statistics ...... 667 13.2.1. Continuous-time time series ...... 667 13.2.2. Discrete-time time series ...... 669 14. Applications to circuits, systems, and control ...... 670 15. Applications to acoustics and mechanics ...... 670 16. Applications to econometrics ...... 671 17. Applications to biology ...... 671 18. Level crossings ...... 671 19. Queueing ...... 671 20. Cyclostationary random fields...... 671 21. Generalizations of cyclostationarity ...... 671 21.1. General aspects ...... 671 ARTICLE IN PRESS
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21.2. Generalized almost-cyclostationary signals ...... 672 21.3. Spectrally correlated signals ...... 672 References ...... 673 Further references ...... 697
1. Introduction autocorrelation functions that are independent of time, depending on only the lag para- Many processes encountered in nature arise meter, and all distinct spectral components are from periodic phenomena. These processes, uncorrelated. although not periodic functions of time, give rise As an alternative, the presence of periodicity in to random data whose statistical characteristics the underlying data-generating mechanism of a vary periodically with time and are called cyclosta- phenomenon can be described without modelling tionary processes [2.5]. For example, in telecom- the available data as a sample path of a stochastic munications, telemetry, radar, and sonar process but, rather, by modelling it as a single applications, periodicity is due to modulation, function of time [4.31]. Within this nonstochastic sampling, multiplexing, and coding operations. In framework, a time-series is said to exhibit second- mechanics it is due, for example, to gear rotation. order cyclostationarity (in the wide sense), as first In radio astronomy, periodicity results from defined in [2.8], if there exists a stable quadratic revolution and rotation of planets and on pulsa- time-invariant transformation of the time-series tion of stars. In econometrics, it is due to that gives rise to finite-strength additive sinewave seasonality; and in atmospheric science it is components. due to rotation and revolution of the earth. In this paper, a concise survey of the literature The relevance of the theory of cyclostationarity (in all languages in which a substantial amount of to all these fields of study and more was first research has been published) on cyclostationarity proposed in [2.5]. is presented and includes an extensive bibliography Wide-sense cyclostationary stochastic processes and list of issued patents. Citations are classified have autocorrelation functions that vary periodi- into 22 categories and listed, for each category, in cally with time. This function, under mild reg- chronological order. In Section 2, general treat- ularity conditions, can be expanded in a Fourier ments and tutorials on the theory of cyclostatio- series whose coefficients, referred to as cyclic narity are cited. General properties of processes autocorrelation functions, depend on the lag para- and time-series are presented in Section 3. In meter; the frequencies, called cycle frequencies, are Section 4, the problem of estimating statistical all multiples of the reciprocal of the period of functions is addressed. Models for manufactured cyclostationarity [2.5]. Cyclostationary processes and natural signals are considered in Sections 5 have also been referred to as periodically correlated and 6, respectively. Communications systems and processes [2.18,3.5]. More generally, if the frequen- related problems are treated in Sections 7–11. cies of the (generalized) Fourier series expansion of Specifically, the analysis and design of commu- the autocorrelation function are not commensu- nications systems is addressed in Section 7, the rate, that is, if the autocorrelation function is an problem of synchronization is addressed in Section almost-periodic function of time, then the process 8, the estimation of signal parameters and wave- is said to be almost-cyclostationary [3.26] or, forms is addressed in Section 9, the identification equivalently, almost-periodically correlated [3.5]. and equalization of channels is addressed in The almost-periodicity property of the autocorre- Section 10, and the signal detection and classifica- lation function is manifested in the frequency tion problems and the problem of source separa- domain as correlation among the spectral com- tion are addressed in Section 11. Periodic ponents of the process that are separated by autoregressive (AR) and autoregressive moving- amounts equal to the cycle frequencies. In contrast average (ARMA) modelling and prediction are to this, wide-sense stationary processes have treated in Section 12. In Section 13, theory and ARTICLE IN PRESS
642 W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 applications of higher-order cyclostationarity are [13.4,13.5], and treated in depth in [13.9,13.13, presented. We address applications to circuits, 13.14,13.17]. An analogous treatment for stochas- systems, and control in Section 14, to acoustics tic processes is given in [13.10]. and mechanics in Section 15, to econometrics in Section 16, and to biology in Section 17. Applica- tions to the problems of level crossing and 3. General properties and structure of stochastic queueing are addressed in Sections 18 and 19, processes and time-series respectively. Cyclostationary random fields are treated in Section 20. In Section 21, some classes 3.1. Introduction of nonstationary signals that extend the class of almost-cyclostationary signals are considered. Fi- General properties of cyclostationary processes nally, some miscellaneous references are listed (see [3.1–3.91]) are derived in terms of the Fourier [22.1–22.8]. Further references only indirectly series expansion of the autocorrelation function. related to cyclostationarity are [23.1–23.15]. The frequencies, called cycle frequencies, are To assist readers in ‘‘going to the source’’, multiples of the reciprocal of the period of seminal contributions—if known— are identified cyclostationarity and the coefficients, referred to within the literature published in English. In some as cyclic autocorrelation functions, are continuous cases, identified sources may have been preceded in functions of the lag parameter. Cyclostationary the literature of another language, most likely processes are characterized in the frequency Russian. For the most part, the subject of this domain by the cyclic spectra, which are the Fourier survey developed independently in the literature transforms of the cyclic autocorrelation functions. published in English. The cyclic spectrum at a given cycle frequency represents the density of correlation between two spectral components of the process that are 2. General treatments separated by an amount equal to the cycle frequency. Almost-cyclostationary processes have General treatments on cyclostationarity are in autocorrelation functions that can be expressed in [2.1–2.18]. The first extensive treatments of the a (generalized) Fourier series whose frequencies theory of cyclostationary processes can be found are possibly incommensurate. in the pioneering works of Hurd [2.1] and Gardner The first contributions to the analysis of the [2.2].In[4.13,2.5,2.11], the theory of second-order general properties of cyclostationary stochastic cyclostationary processes is developed mainly with processes are in the Russian literature [3.1–3.3, reference to continuous-time stochastic processes, 3.5,3.7–3.9]. The problem of spectral analysis is but discrete-time is the focus in [4.13]. Discrete- mainly treated in [3.10,3.11,3.32,3.35,3.51,3.53, time processes are treated more generally in [2.17] 3.61,3.68,3.69,3.80,3.88]. The stationarizing effects in a manner largely analogous to that in [2.5]. The of random shifts are examined in [3.20,3.26,3.57] statistical characterization of cyclostationary time- and the important impact of random shifts on series in the nonstochastic framework is intro- cyclo-ergodic properties is exposed in [2.15]. The duced and treated in depth [2.6,2.8,2.12,2.14] with problem of filtering is considered in [3.9,3.13,3.67]. reference to continuous-time signals and in [2.15] The mathematical link between the stochastic for both continuous- and discrete-time signals. and nonstochastic approaches, which was first The case of complex signals is introduced and established in [2.5,2.12], is rigorously treated in treated in depth in [2.8,2.9]. Finally, a rigorous [3.87]. Wavelet analysis of cyclostationary pro- treatment of periodically correlated processes cesses is addressed in [3.70,3.81]. within the framework of harmonizable processes For further-related references, see the general is given in [2.18]. treatments in [2.1,2.2,2.4–2.8,2.11–2.13,2.15,2.18], The theory of higher-order cyclostationarity in and also [4.13,4.31,4.41,13.2,13.3,13.6,16.3,18.3, the nonstochastic framework is introduced in 21.9,21.14]. ARTICLE IN PRESS
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3.2. Stochastic processes frequencies. Wide-sense cyclostationary processes have also been called periodically correlated 3.2.1. Continuous-time processes processes (see e.g., [2.1,3.3,3.59]). As first shown Let us consider a continuous-time real-valued in [3.23], xðtÞ and its frequency-shifted version stochastic process fxðt; oÞ; t 2 R; o 2 Og, with ab- xðtÞej2pnt=T0 are correlated. The wide-sense station- breviated notation xðtÞ when this does not create ary processes are the special case of cyclostation- n=T0 c ambiguity, defined on a probability space ary processes for which Rx ðtÞ 0 only for ðO; F; PÞ, where O is the sample space, equipped n ¼ 0. It can be shown that if xðtÞ is cyclosta- with the s-field F,andP is a probability measure tionary with period T 0, then the stochastic process defined on the elements of F. xðt þ yÞ, where y is a random variable that is The process xðtÞ is said to be Nth-order uniformly distributed in ½0; T0Þ and is statistically cyclostationary in the strict sense [2.2,2.5] if its independent of xðtÞ, is wide sense stationary Nth-order distribution function [2.5,3.20,3.26,3.57]. A more general class of stochastic processes is F ðx ; ...; x ; x Þ xðtþt1Þ xðtþtN 1ÞxðtÞ 1 N 1 N obtained if the autocorrelation function Rxðt; tÞ is 9Pfxðt þ t1Þpx1; ...; xðt þ tN 1Þ almost periodic in t for each t. A function zðtÞ is said to be almost periodic if it is pxN 1; xðtÞpxN gð3:1Þ the limit of a uniformly convergent sequence of is periodic in t with some period, say T 0: trigonometric polynomials in t [23.2,23.3,23.4, Paragraphs 24–25,23.6,23.7, Part 5, 23.11]: F xðtþt1þT0Þ xðtþtN 1þT0ÞxðtþT0Þðx1; ...; xN 1; xN Þ X zðtÞ¼ z ej2pat, (3.8) ¼ F xðtþt1Þ xðtþtN 1ÞxðtÞðx1; ...; xN 1; xN Þ a N 1 a2A 8t 2 R 8ðt1; ...; tN 1Þ2R where A is a countable set, the frequencies a 2 A 8ð Þ2 N ð Þ x1; ...; xN R . 3:2 are possibly incommensurate, and the coefficients The process xðtÞ is said to be second-order za are given by cyclostationary in the wide sense [2.2,2.5] if its j2pat za9hzðtÞe it mean EfxðtÞg and autocorrelation function Z 1 T=2 ¼ lim zðtÞe j2pat dt. ð3:9Þ Rxðt; tÞ9Efxðt þ tÞxðtÞg (3.3) T!1 T T=2 are periodic with some period, say T : 0 Such functions are called almost-periodic in the
Efxðt þ T 0Þg ¼ EfxðtÞg, (3.4) sense of Bohr [23.3, Paragraphs 84–92] or, equivalently, uniformly almost periodic in t in the sense of Besicovitch [23.2, Chapter 1]. Rxðt þ T0; tÞ¼Rxðt; tÞ (3.5) The process xðtÞ is said to be Nth-order almost- for all t and t. Therefore, by assuming that the cyclostationary in the strict sense [2.2,2.5] if its Nth- Fourier series expansion of Rxðt; tÞ is convergent order distribution function (3.1) is almost-periodic to Rxðt; tÞ, we can write in t. With reference to the autocorrelation proper- Xþ1 ties, a continuous-time real-valued stochastic pro- n=T0 j2pðn=T0Þt Rxðt; tÞ¼ Rx ðtÞe , (3.6) cess xðtÞ is said to be almost-cyclostationary (ACS) n¼ 1 in the wide sense [2.2,2.5,3.26] if its autocorrelation where the Fourier coefficients function Rxðt; tÞ is an almost periodic function of t Z (with frequencies not depending on t). Thus, it is 1 T0=2 the limit of a uniformly convergent sequence of Rn=T0 ðtÞ9 R ðt; tÞe j2pðn=T0Þt dt (3.7) x T x trigonometric polynomials in t: 0 T0=2 X a j2pat are referred to as cyclic autocorrelation functions Rxðt; tÞ¼ RxðtÞe ,(3.10) 2 and the frequencies fn=T0gn2Z are called cycle a A ARTICLE IN PRESS
644 W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 where tive sinewave component: Z 1 T=2 j2pat a 9 j2pat hrxðt; tÞe it ¼ 0 8a 2 R. (3.16) RxðtÞ lim Rxðt; tÞe dt (3.11) T!1 T T=2 In the special case where limjtj!1 rxðt; tÞ¼0, xðtÞ is the cyclic autocorrelation function at cycle is said to be asymptotically almost cyclostationary frequency a. As first shown in [3.26],ifxðtÞ is an [3.26]. ACS process, then the process xðtÞ and its Let us now consider the second-order (wide- frequency-shifted version xðtÞej2pat are correlated sense) characterization of ACS processes in the when a 2 A. Wide-sense almost-cyclostationary frequency domain. Let processes have also been called almost-periodically Z correlated processes (see e.g., [2.1,3.5,3.59]). The Xðf Þ9 xðtÞe j2pft dt (3.17) wide-sense cyclostationary processes are obtained R as a special case of the ACS processes when A be the stochastic process obtained from Fourier fn=T 0gn2Z for some T 0. transformation of the ACS process xðtÞ, where the Let At be the set Fourier transform is assumed to exist, at least in 9 a a the sense of distributions (generalized functions) At fa 2 R : RxðtÞ 0g. (3.12) [23.10], with probability 1. By using (3.10), in the In [3.59], it is shown that the ACS processes are sense of distributions we obtain characterized by the following conditions: X a EfXðf 1ÞX ðf 2Þg ¼ Sxðf 1Þdðf 2 f 1 þ aÞ, (1) The set a2A [ (3.18) A9 At (3.13) t2R where dð Þ is the Dirac delta, superscript is is countable. complex conjugation, and Z (2) The autocorrelation function Rxðt; tÞ is uni- a 9 a j2pf t formly continuous in t and t. Sxðf Þ RxðtÞe dt (3.19) (3) The time-averaged autocorrelation function R 0 9 RxðtÞ hRxðt; tÞit is continuous for t ¼ 0 is referred to as the cyclic spectrum at cycle (and, hence, for every t). frequency a. Therefore, for an ACS process, (4) The process is mean-square continuous, that is correlation exists between spectral components sup Efjxðt þ tÞ xðtÞj2g!0ast ! 0. that are separated by amounts equal to the cycle t2R frequencies. The support in the ðf 1; f 2Þ plane of the (3.14) spectral correlation function E Xðf 1ÞX ðf 2Þ con- sists of parallel lines with unity slope. The density of spectral correlation on this support is described More generally, a stochastic process xðtÞ is said to by the cyclic spectra aðf Þ, a 2 A, which can be exhibit cyclostationarity at cycle frequency a if Sx expressed as [2.5] RaðtÞc0 [2.5]. In such a case, the autocorrelation x Z function can be expressed as T=2 X a 1 Sxðf Þ¼ lim lim EfDfX 1=Df ðt; f Þ a j2pat Df !0 T!1 T Rxðt; tÞ¼ RxðtÞe þ rxðt; tÞ, (3.15) T=2 a2A X 1=Df ðt; f aÞg dt, ð3:20Þ where the function X where the order of the two limits cannot be a j2pat RxðtÞe reversed, and a2A Z tþZ=2 is not necessarily continuous in t and the term j2pfs X Zðt; f Þ9 xðsÞe ds. (3.21) rxðt; tÞ does not contain any finite-strength addi- t Z=2 ARTICLE IN PRESS
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a Therefore, the cyclic spectrum Sxðf Þ is also called ACS, then it follows that [2.1,2.18,3.59] the spectral correlation density function. It repre- X ðf ; f Þ¼ aðf Þdðf f þ aÞ df df . sents the time-averaged statistical correlation (with dg 1 2 Sx 1 2 1 1 2 a2A zero lag) of two spectral components at frequen- cies f and f a, as the bandwidth approaches (3.26) zero. For a ¼ 0, the cyclic spectrum reduces to the Finally, note that symmetric definitions of cyclic 0 power spectrum or spectral density function Sxðf Þ autocorrelation function and cyclic spectrum have and (3.19) reduces to the Wiener–Khinchin Rela- been widely used (see, e.g., [2.5,2.8,2.11]). They are tion. Consequently, when (3.19) and (3.20) was linked to the asymmetric definitions (3.11) and discovered in [2.5] it was dubbed the Cyclic (3.20) by the relationships Wiener–Khinchin Relation. Z 1 T=2 In contrast, for wide-sense stationary processes lim Efxðt þ t=2Þxðt t=2Þg the autocorrelation function does not depend on t, T!1 T T=2 j2pat a jpat 0 e dt ¼ RxðtÞe ð3:27Þ Efxðt þ tÞxðtÞg ¼ RxðtÞ (3.22) and and, equivalently, no correlation exists between Z distinct spectral components, 1 T=2 lim lim Df EfX 1=Df ðt; f þ a=2Þ 0 Df !0 T!1 T T=2 EfXðf 1ÞX ðf 2Þg ¼ Sxðf 1Þdðf 2 f 1Þ. (3.23) X ðt f Þg t ¼ aðf þ Þ ð Þ A covariance (or autocorrelation) function 1=Df ; a=2 d Sx a=2 , 3:28 Efxðt1Þx ðt2Þg is said to be harmonizable if it can respectively. be expressed as Z 3.2.2. Discrete-time processes j2pðf 1t1 f 2t2Þ Efxðt1Þx ðt2Þg ¼ e dgðf 1; f 2Þ, (3.24) R2 Let us consider a discrete-time real-valued stochastic process fxðn; oÞ; n 2 Z; o 2 Og, with where gðf ; f Þ is a covariance of bounded varia- 1 2 abbreviated notation xðnÞ when this does not tion on R R and the integral is a Fourier– create ambiguity. The stochastic process xðnÞ is Stieltjes transform [23.5]. Moreover, a second- said to be second-order almost-cyclostationary in order stochastic process xðtÞ is said to be the wide sense [2.2,2.5,4.13] if its autocorrelation harmonizable if there exists a second-order sto- function chastic process wðf Þ with covariance function e Efwðf 1Þw ðf 2Þg ¼ gðf 1; f 2Þ of bounded variation Rxðn; mÞ9Efxðn þ mÞxðnÞg (3.29) on R R such that Z is an almost-periodic function of the discrete-time parameter n. Thus, it can be expressed as xðtÞ¼ ej2pft dwðf Þ (3.25) X R ea e e ðn; mÞ¼ e ðmÞej2pan, (3.30) with probability one. In [23.5], it is shown that a Rx Rx e necessary condition for a stochastic process to be ea2A harmonizable is that it be second-order contin- where uous. Moreover, it is shown that a stochastic e XN process is harmonizable if and only if its covar- e a 9 1 e j2pean RxðmÞ lim Rxðn; mÞe N!1 þ iance is harmonizable. If a stochastic process 2N 1 n¼ N is harmonizable, in the sense of distributions (3.31) [23.10], we have dwðf Þ¼Xðf Þ df and dgðf 1; f 2Þ¼ Efdwðf Þ dw ðf Þg ¼ EfXðf ÞX ðf Þg df df ,and is the cyclic autocorrelation function at cycle 1 2 1 2 1 2 e wðf Þ is the indefinite integral of Xðf Þ or the frequency a and integrated Fourier transform of xðtÞ [23.4]. There- e e9 e 1 1 e a c fore, if the stochastic process is harmonizable and A fa 2½ 2; 2Þ : RxðmÞ 0g (3.32) ARTICLE IN PRESS
646 W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 is a countable set. Note that the cyclic autocorre- proach turns out to be more appropriate when an ea ensemble of realizations does not exist and would lation function e ðmÞ is periodic in ea with period Rx have to be artificially introduced just to create a 1. Thus, the sum in (3.30) can be equivalently e mathematical model, that is, the stochastic pro- e 9 e e a c cess. Such a model can be unnecessarily abstract extended to the set A1 fa 2½0; 1Þ : RxðmÞ 0g. e f when there is only a single time series at hand. In general, the set A (or A1) contains possibly incommensurate cycle frequencies ea. In the special In the FOT probability approach, probabilistic parameters are defined through infinite-time Ae f N ðN Þ N g case where 1 0; 1= 0; ...; 0 1 = 0 for averages of a single time series (and functions of some integer N0, the autocorrelation function e this time series) rather than through expected Rxðn; mÞ is periodic in n with period N0 and the values or ensemble averages of a stochastic process xðnÞ is said to be cyclostationary in the wide process. Moreover, starting from this single time sense.IfN0 ¼ 1 then xðnÞ is wide-sense stationary. series, a (possibly time varying) probability dis- Let tribution function can be constructed and this X XeðnÞ9 xðnÞe j2pnn (3.33) leads to an expectation operation and all the n2Z associated familiar probabilistic concepts and parameters, such as stationarity, cyclostationarity, be the stochastic process obtained from Fourier nonstationarity, independence, mean, variance, transformation (in a generalized sense) of the ACS moments, cumulants, etc. For comprehensive process xðnÞ. By using (3.30), in the sense of treatments of the FOT probability framework see distributions it can be shown that [3.59] [2.8,2.12,2.15] and, for more mathematical rigor e e on foundations and existence proofs, see [23.15]. EfXðn1ÞX ðn2Þg X e X The extension of the Wold isomorphism to e a e cyclostationary sequences was first introduced in ¼ Sxðn1Þ dðn2 n1 þ a ‘Þ, ð3:34Þ ‘2Z [2.5], treated more in depth in [2.12], and finally— ea2Ae with mathematical rigor—in [3.87]. where The time-variant FOT probability framework is e X e based on the decomposition of functions of a time e a 9 e a j2pnm SxðnÞ RxðmÞe (3.35) series into their (possibly zero) almost-periodic m2Z components and residual terms. Starting from is the cyclic spectrum at cycle frequency ea. The such a decomposition, the expectation operator is ea defined. Specifically, for any finite-average-power e ð Þ e cyclic spectrum Sx n is periodic in both n and a time series xðtÞ, let us consider the decomposition with period 1. In [3.3,4.41], it is shown that discrete-time xðtÞ9xapðtÞþxrðtÞ, (3.36) cyclostationary processes are harmonizable. where xapðtÞ is an almost-periodic function and xrðtÞ a residual term not containing finite-strength 3.3. Time series additive sinewave components; that is, hx ðtÞe j2pati 0 8a 2 R. (3.37) 3.3.1. Continuous-time time series r t A statistical analysis framework for time series The almost-periodic component extraction operator that is an alternative to the classical stochastic- Efagf g is defined to be the operator that extracts all process framework is the fraction-of-time (FOT) the finite-strength additive sinewave components probability framework first introduced for ACS of its argument, that is, time series in [2.5,2.8,2.12]; see also [2.15]. In the EfagfxðtÞg9x ðtÞ. (3.38) FOT probability framework, signals are modelled ap as single functions of time (time series) rather than Let xðtÞ, t 2 R, be a real-valued continuous-time sample paths of stochastic processes. This ap- time series (a single function of time) and let us ARTICLE IN PRESS
W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 647 assume that the set G1 of frequencies (for every x) let us assume that the set G2 of frequencies (for of the almost-periodic component of the function every x1; x2 and t) of the almost-periodic compo- of t 1fxðtÞpxg is countable, where nent of the function of t 1fxðtþtÞpx1g1fxðtÞpx2g is ( countable. Then, the function of x1 and x2 1; t : xðtÞpx; 9 1fxðtÞpxg (3.39) fag 0; t : xðtÞ4x F xðtþtÞxðtÞðx1; x2Þ fag 9E f1fxðtþtÞ x g1fxðtÞ x ggð3:43Þ is the indicator function of the set ft 2 R : xðtÞpxg. p 1 p 2 In [2.12] it is shown that the function of x is a valid second-order joint cumulative distribu- F fag ðxÞ9Efagf1 g (3.40) tion function for every fixed t and t, except for the xðtÞ fxðtÞpxg right-continuity property (in the discontinuity for any t is a valid cumulative distribution func- points) with respect to x1 and x2. Moreover, the second-order derivative, with respect to x1 and x2, tion except for the right-continuity property (in fag fag the discontinuity points). That is, it has values of F xðtþtÞxðtÞðx1; x2Þ, denoted by f xðtþtÞxðtÞðx1; x2Þ,is fag a valid second-order joint probability density in ½0; 1 , is non decreasing, F xðtÞð 1Þ ¼ 0, and fag function [2.12]. Furthermore, it can be shown that F xðtÞðþ1Þ ¼ 1. Moreover, its derivative with res- fag the function pect to x, denoted by f xðtÞðxÞ, is a valid probability density function and, for any well-behaved func- 9 fag tion gð Þ, it follows that Rxðt; tÞ E fxðt þ tÞxðtÞg (3.44) Z is a valid autocorrelation function and can be EfagfgðxðtÞÞg ¼ gðxÞf fag ðxÞ dx (3.41) xðtÞ characterized by R Z fag which reveals that E f g is the expecta- fag Rxðt; tÞ¼ x1x2f xðtþtÞxðtÞðx1; x2Þ dx1 dx2 tion operator with respect to the distribution R2 fag X function F xðtÞðxÞ for the time series xðtÞ. The a j2pat ¼ RxðtÞe , ð3:45Þ result (3.41), first introduced in [2.8], is referred a2A to as the fundamental theorem of temporal expecta- tion, by analogy with the corresponding funda- where A is a countable set and mental theorem of expectation from probability a 9 j2pat theory. RxðtÞ hxðt þ tÞxðtÞe it (3.46) For an almost-periodic signal xðtÞ,wehave xðtÞ xapðtÞ and, hence, is the (nonstochastic) cyclic autocorrelation func- fag tion at cycle frequency a ða 2 RÞ. E fxðtÞg ¼ xðtÞ. (3.42) The classification of the kind of nonstationarity That is, the almost-periodic functions are the of a time series is made on the basis of the elements deterministic signals in the FOT probability contained in the set A. In general, the set A can framework. All the other signals are the random contain incommensurate cycle frequencies a and, signals. Note that the term ‘‘random’’ here is not in such a case, the time series is said to be wide- intended to be synonymous with ‘‘stochastic’’. In sense almost cyclostationary. In the special case fact, the adjective stochastic is adopted, as usual, where A fk=T 0gk2Z the time series xðtÞ is said to when an ensemble of realizations or sample paths be wide-sense cyclostationary. If the set A contains exists, whereas the adjective random is used in only the element a ¼ 0, then the time series xðtÞ is reference to a single function of time. said to be wide-sense stationary. Analogously, a second-order characterization Finally, note that the periodic component with for the real-valued time series xðtÞ can be obtained period T 0 of an almost-periodic time series (or lag by using the almost-periodic component extraction product time series) zðtÞ can be extracted by operator as the expectation operator. Specifically, exploiting the synchronized averaging identity ARTICLE IN PRESS
648 W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 introduced in [2.5,2.8]: the right-continuity property (in the discontinuity feag Xþ1 points) with respect to x1 and x2. In (3.50), E f g j2pðk=T0Þt denotes the discrete-time almost-periodic compo- zk=T0 e k¼ 1 nent extraction operator, which is defined analo- 1 XN gously to its continuous-time counterpart. The ¼ lim zðt nT 0Þ, ð3:47Þ second-order derivative with respect to x1 and x2 N!1 2N þ 1 n¼ N feag feag of F xðnþmÞxðnÞðx1; x2Þ, denoted by f xðnþmÞxðnÞðx1; x2Þ, where the Fourier coefficients z are defined k=T0 is a valid second-order joint probability density according to (3.9). function [2.12]. Furthermore, it can be shown that ACS time series are characterized in the spectral the function domain by the (nonstochastic) cyclic spectrum or spectral correlation density function at cycle fre- e Re ðn; mÞ9Efagfxðn þ mÞxðnÞg (3.51) quency a: x Z T=2 is a valid autocorrelation function and can be a 9 1 Sxðf Þ lim lim Df characterized by Df !0 T!1 T T=2 Z X ðt; f ÞX ðt; f aÞ dt, ð3:48Þ 1=Df 1=Df e feag Rxðn; mÞ¼ x1x2f xðnþmÞxðnÞðx1; x2Þ dx1 dx2 where X ðt; f Þ is defined according to (3.21) and R2 1=Df X ea e the order of the two limits cannot be reversed. The ¼ Re ðmÞej2pan, ð3:52Þ Cyclic Wiener Relation introduced in [2.8] x Z ea2Ae a a j2pf t Sxðf Þ¼ RxðtÞe dt (3.49) R where links the cyclic autocorrelation function to the e e9 e 1 1 ea c cyclic spectrum. This relation generalizes that for A fa 2½ 2; 2Þ : RxðmÞ 0g (3.53) a ¼ 0, which was first dubbed the Wiener Relation in [2.5] to distinguish it from the Khinchin Relation is a countable set and (3.19), which is frequently called the Wiener– XN Khinchin Relation. ea e 9 1 j2pean RxðmÞ lim xðn þ mÞxðnÞe N!1 þ 2N 1 n¼ N 3.3.2. Discrete-time time series (3.54) The characterization of discrete-time time series (sequences) is similar to that of continuous-time is the (nonstochastic) discrete-time cyclic autocor- time series. We consider here only the wide-sense relation function at cycle frequency ea. second-order characterization. Obviously, as in the stochastic framework, the Let xðnÞ, n 2 Z, be a real-valued discrete-time e e ea time series. Let us assume that the set G2 of cyclic autocorrelation function RxðmÞ is periodic in e frequencies (for every x1; x2 and m) of the almost- a with period 1. Thus, the sum in (3.52) can be e periodic component of the function of equivalently extended to the set A19fea 2½0; 1Þ : n 1 1 is countable. Then, the ea fxðnþmÞpx1g fxðnÞpx2g Re ðmÞc g function of x and x x 0 . Moreover, as in the continuous-time 1 2 case, the classification of the kind of nonstationarity e F fag ðx ; x Þ of discrete-time time series is made on the basis of xðnþmÞxðnÞ 1 2 e e the elements contained in set A. That is, in general, 9Efagf1 1 gð3:50Þ fxðnþmÞpx1g fxðnÞpx2g set Ae can contain incommensurate cycle frequencies is a valid second-order joint cumulative distribu- ea and, in such a case, the time series is said to be tion function for every fixed n and m, except for wide-sense almost cyclostationary. In the special case ARTICLE IN PRESS
W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 649
e where A1 f0; 1=N0; ...; ðN0 1Þ=N0g for some ties (see Section 4), the stochastic and FOT integer N0, the time series xðnÞ is said to be wide- autocorrelation functions are identical for almost sense cyclostationary.IfthesetAe contains only the all sample paths xðtÞ, e element a ¼ 0, then the time series xðnÞ is said to be Rxðt; tÞ9Efxðt þ tÞxðtÞg wide-sense stationary. ¼ Efagfxðt þ tÞxðtÞg9R ðt; tÞð3:58Þ Discrete-time ACS time series are characterized x in the spectral domain by the (nonstochastic) and, hence, so too are their cyclic components and cyclic spectrum or spectral correlation density frequency-domain counterparts, function at cycle frequency ea: a a RxðtÞ¼RxðtÞ, (3.59) e XN ea 9 1 SxðnÞ lim lim Dn Dn!0 N!1 þ 2N 1 n¼ N a a Sxðf Þ¼Sxðf Þ. (3.60) e X b1=Dncðn; nÞX b1=Dncðn; n aÞ, ð3:55Þ Analogous equivalences hold in the discrete-time where case. The link between the two approaches is treated nXþM in depth in [2.5,2.8,2.9,2.11,2.12,2.15,3.87,4.31, ð Þ9 ð Þ j2pnk X 2Mþ1 n; n x k e (3.56) 23.15]. In the following, most results are presented ¼ k n M in the FOT probability framework. and b c denotes the closest odd integer. The Cyclic Wiener relation [2.5] 3.5. Complex processes and time series X ea ea The case of complex-valued processes and time Se ðnÞ¼ Re ðmÞe j2pnm (3.57) x x series, first treated in depth in [2.9], is extensively m2Z treated in [2.6,2.8,3.43,13.13,13.14,13.20,13.25]. links the cyclic autocorrelation function to the Several results with reference to higher-order cyclic spectrum. statistics are reported in Section 13. Let xðtÞ be a zero-mean complex-valued con- tinuous-time time series. Its wide-sense character- 3.4. Link between the stochastic and fraction-of- ization can be made in terms of the two second- time approaches order moments fag In the time-variant nonstochastic framework R ðt; tÞ9E fxðt þ tÞx ðtÞg xx X (for ACS time series), the almost-periodic func- a j2pat ¼ R ðtÞe , ð3:61Þ tions play the same role as that played by the xx a2A deterministic functions in the stochastic-process xx framework, and the expectation operator is the fag Rxxðt; tÞ9E fxðt þ tÞxðtÞg almost-periodic component extraction operator. X b j2pbt Therefore, in the case of processes exhibiting ¼ RxxðtÞe ð3:62Þ suitable ergodicity properties, results derived in b2Axx the FOT probability approach for time series can which are called the autocorrelation function and be interpreted in the classical stochastic process conjugate autocorrelation function, respectively. framework by substituting, in place of the almost- The Fourier coefficients periodic component extraction operator Efagf g, a 9 j2pat the statistical expectation operator Ef g. In fact, by Rxx ðtÞ hxðt þ tÞx ðtÞe it, (3.63) assuming that fxðt; oÞ; t 2 R; o 2 Og is a stochastic b 9 j2pbt process satisfying appropriate ergodicity proper- RxxðtÞ hxðt þ tÞxðtÞe it (3.64) ARTICLE IN PRESS
650 W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 are referred to as the cyclic autocorrelation function More general time-variant linear filtering is ad- at cycle frequency a and the conjugate cyclic dressed in [21.10,21.11]. autocorrelation function at conjugate cycle fre- quency b, respectively. The Fourier transforms of 3.6.1. Structure of linear almost-periodically time- the cyclic autocorrelation function and conjugate variant systems cyclic autocorrelation function A linear time-variant system with input xðtÞ, Z output yðtÞ, impulse-response function hðt; uÞ, and a 9 a j2pf t Sxx ðf Þ Rxx ðtÞe dt, (3.65) input–output relation R Z Z yðtÞ¼ hðt; uÞxðuÞ du (3.69) b 9 b j2pf t R Sxxðf Þ Rxxðf Þe dt (3.66) R is said to be linear almost-periodically time-variant are called the cyclic spectrum and the conjugate (LAPTV) if the impulse-response function admits cyclic spectrum, respectively. the Fourier series expansion ð Þ X Let us denote by the superscript an optional j2psu complex conjugation. In the following, when it hðt; uÞ¼ hsðt uÞe , (3.70) does not create ambiguity, both functions s2G defined in (3.63) and (3.64) are simultaneously where G is a countable set. represented by By substituting (3.70) into (3.69) we see that the output yðtÞ can be expressed in the two equivalent a ð Þ9 ð þ Þ ð Þð Þ j2pat 2 Rxxð Þ t x t t x t e t; a Axxð Þ . forms [2.8,9.51]: X (3.67) j2pst yðtÞ¼ hsðtÞ ½xðtÞe (3.71a) Analogously, both functions defined in (3.65) and s2G (3.66) are simultaneously represented by X Z j2pst ¼ ½gsðtÞ xðtÞ e , (3.71b) a 9 a j2pf t s2G Sxxð Þ ðf Þ Rxxð Þ ðtÞe dt. (3.68) R where It should be noted that, in [2.6,2.8,2.9], for 9 j2pst example, a different conjugation notation in the gsðtÞ hsðtÞe . (3.72) subscripts is adopted to denote the autocorrelation From (3.71a) it follows that a LAPTV systems and the conjugate autocorrelation function. Spe- performs a linear time-invariant filtering of fag cifically, Rxxðt; tÞ¼E fxðt þ t=2Þx ðt t=2Þg and frequency-shifted version of the input signal. fag Rxx ðt; tÞ¼E fxðt þ t=2Þxðt t=2Þg. Moreover, For this reason LAPTV filtering is also referred an analogous notation is adopted in these refer- to as frequency-shift (FRESH) filtering [7.31]. ences and others for the (conjugate) cyclic auto- Equivalently, from (3.71b) it follows that a correlation function and the (conjugate) cyclic LAPTV systems performs a frequency shift spectrum. of linear time-invariant filtered versions of the input. 3.6. Linear filtering In the special case for which G fk=T 0gk2Z for some period T 0, the system is said to be linear The linear almost-periodically time-variant fil- periodically time-variant (LPTV). If G contains tering of ACS signals introduced in [2.2] and only the element s ¼ 0, then the system is linear followed by [2.5] for cyclostationary processes and time-invariant (LTI). generalized in [2.8,2.9] to ACS signals, is also considered in follow-on work in [7.60,9.51,13.9, 3.6.2. Input/output relations in terms of cyclic 13.14,13.20] as well as the early Russian work in statistics [3.9]. Properties of linear periodically time-varying Let xiðtÞ, i ¼ 1; 2, t 2 R, be two possibly- systems are analyzed in [23.8,23.12,23.13,23.14]. complex ACS continuous-time time series with ARTICLE IN PRESS
W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 651 Z second-order (conjugate) cross-correlation func- Sb ðf Þ9 Rb ðtÞe j2pf t dt tion y yð Þ y yð Þ 1 2 XR 1X2 fag ð Þ b s1 ð Þs2 ð Þ9 f ð þ Þ ð Þg ¼ S ð Þ ðf s1Þ R ð Þ t; t E x1 t t x2 t x x x1x 1 2 2 X s12G1 s22G2 ¼ Ra ðtÞej2pat, ð3:73Þ ð Þ x xð Þ Hs ðf ÞH ðð Þðb f ÞÞ, ð3:81Þ 1 2 1 s2 a2A12 where where Z a ð Þ j2pat j2pf t R ð Þ ðtÞ9hx1ðt þ tÞx ðtÞe i (3.74) H ðf Þ9 h ðtÞe dt (3.82) x x 2 t si si 1 2 R is the (conjugate) cyclic cross-correlation between and, in the sums in (3.80) and (3.81), only those x1 and x2 at cycle frequency a and s1 2 G1 and s2 2 G2 such that b s1 ð Þs2 2 9 a c A12 fa 2 R : R ð Þ ðtÞ 0g (3.75) A12 give nonzero contribution. x1x 2 Eqs. (3.80) and (3.81) can be specialized to is a countable set. If the set A12 contains at least one nonzero element, then the time series several cases of interest. For example, if x1 ¼ x2 ¼ x, h1 ¼ h2 ¼ h, y1 ¼ y2 ¼ y,andð Þ is x1ðtÞ and x2ðtÞ are said to be jointly ACS. Note conjugation, then we obtain the input–output that, in general, set A12 depends on whether ð Þ is conjugation or not and can be different from relations for LAPTV systems in terms of cyclic autocorrelation functions and cyclic spectra: the sets A11 and A22 (both defined according to X X (3.75)). b b s1þs2 j2ps1t Ryy ðtÞ¼ ½Rxx ðtÞe Let us consider now two linear LAPTV systems s12G s22G whose impulse-response functions admit the Four- b r12ðtÞ, ð3:83Þ ier series expansionsX t j2psiu X X hiðt; uÞ¼ hs ðt uÞe ; i ¼ 1; 2. (3.76) i b b s1þs2 ð Þ¼ ð Þ si2Gi Syy f Sxx f s1 s12G s22G The (conjugate) cross-correlation of the outputs Z H ðf ÞH ðf bÞ, ð3:84Þ s1 s2 y ðtÞ¼ h ðt; uÞx ðuÞ du; i ¼ 1; 2 (3.77) i i i where R Z is given by b j2pbs r ðtÞ9 hs ðt þ sÞh ðsÞe ds. (3.85) fag ð Þ 12 1 s2 R ð Þ ðt; tÞ9E fy ðt þ tÞy ðtÞg R y y 1 2 1 2 X X X For further examples and applications, see Sec- ¼ ½Ra ðtÞej2ps1t x xð Þ 1 2 tions 7 and 10. a2A12 s12G1 s22G2
aþs1þð Þs2 j2pðaþs1þð Þs2Þt rs s ð Þ ðtÞe , ð3:78Þ t 1 2 3.7. Product modulation where denotes convolution with respect to t, ð Þ t Let xðtÞ and cðtÞ be two ACS signals with is an optional minus sign that is linked to ð Þ,and Z (conjugate) autocorrelation functions g 9 ð Þ j2pgs X rs s ð ÞðtÞ hs1 ðt þ sÞhs ðsÞe ds. (3.79) ax j2paxt 1 2 2 R ð Þ ðt; tÞ¼ R ðtÞe , (3.86) R xx xxð Þ a 2A Thus, x xxð Þ b ð Þ X 9 j2pbt a j2pa t R ð Þ ðtÞ hy1ðt þ tÞy ðtÞe it c c y y 2 Rccð Þ ðt; tÞ¼ R ð Þ ðtÞe . (3.87) 1 2 X X cc ð Þ ac2A ð Þ ¼ ½Rb s1 s2 ðtÞej2ps1t cc x xð Þ 1 2 s12G1 s22G2 If xðtÞ and cðtÞ are statistically independent in the b FOT probability sense, then their joint probability rs s ð ÞðtÞ, ð3:80Þ t 1 2 density function factors into the product of the ARTICLE IN PRESS
652 W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 marginal probability densities [2.8,2.9,2.12] and From (3.96) it follows that the support in the ða; f Þ the (conjugate) autocorrelation functions of the plane of the (conjugate) cyclic spectrum of yðtÞ is product waveform such that yðtÞ¼cðtÞxðtÞ (3.88) a 9 a a supp½Syyð Þ ðf Þ fða; f Þ2R R : Syyð Þ ðf Þ 0g also factor, fða; f Þ2R R : Hðf Þ ð Þ Ryyð Þ ðt; tÞ¼Rccð Þ ðt; tÞRxxð Þ ðt; tÞ. (3.89) H ðð Þða f ÞÞa0g. ð3:97Þ Therefore, the (conjugate) cyclic autocorrelation Let xðtÞ be a strictly band-limited low-pass signal function and the (conjugate) cyclic spectrum of 0 with monolateral bandwidth B; that is, Sxx ðf Þ 0 yðtÞ are [2.5,2.8]: for f eð B; BÞ. Then, X Ra ðtÞ¼ Rax ðtÞRa ax ðtÞ, (3.90) yyð Þ xxð Þ ccð Þ xðtÞ xðtÞ hLPFðtÞ, (3.98) ax2A ð Þ xx where h ðtÞ is the impulse-response function of Z LPF X the ideal low-pass filter with harmonic-response Sa ðf Þ¼ Sax ðlÞSa ax ðf lÞ dl, yyð Þ xxð Þ ccð Þ function: a 2A R x xxð Þ ( f 1; jf jpB; (3.91) H ðf Þ¼rect 9 (3.99) LPF 2B 0; jf j4B: where, in the sums, only those (conjugate) cycle frequencies ax such that a ax 2 Accð Þ give non- Accounting for (3.97), we have (see Fig. 1) zero contribution. a Observe that, if cðtÞ is an almost-periodic supp½Sxxð Þ ðf Þ fða; f Þ2R R : HLPFðf Þ function ð Þa g ð Þ X HLPF f a 0 , 3:100 j2pgt cðtÞ¼ cge , (3.92) where the fact that rectðf Þ is real and even is g2G used. then ð Þ R ð Þ ðt; tÞ¼cðt þ tÞc ðtÞ cc X X ¼ c cð Þeð Þj2pg2t g1 g2 2B g12G g22G ej2pðg1þð Þg2Þt ð3:93Þ and X a ð Þ j2pða gÞt Rccð Þ ðtÞ¼ cgcð Þða gÞe , (3.94) g2G X ð Þ a − Sccð Þ ðf Þ¼ cgcð Þða gÞdðf þ g aÞ. (3.95) B B f g2G
3.8. Supports of cyclic spectra of band limited signals
By specializing (3.81) to the case x ¼ x ¼ x, 1 2 −2B h1 ¼ h2 ¼ h (LTI), and y1 ¼ y2 ¼ y, we obtain Sa ðf Þ¼Sa ðf ÞHðf ÞHð Þðð Þða f ÞÞ. (3.96) yyð Þ xxð Þ Fig. 1. Cyclic-spectrum support of a low-pass signal. ARTICLE IN PRESS
W.A. Gardner et al. / Signal Processing 86 (2006) 639–697 653
Let xðtÞ be a strictly band-limited high-pass 0 signal; that is, Sxx ðf Þ 0 for f 2ð b; bÞ. Then, 2B xðtÞ xðtÞ hHPFðtÞ, (3.101) where hHPFðtÞ is the impulse-response function of the ideal high-pass filter with harmonic-response function 2b f H ðf Þ¼1 rect . (3.102) HPF 2b −B −b b B f From (3.97), we have (see Fig. 2)
a − supp½Sxxð Þ ðf Þ fða; f Þ2R R : HHPFðf Þ 2b