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MC1374 TV Modulator Circuit

The MC1374 includes an FM audio modulator, sound carrier oscillator, RF oscillator, and RF dual input modulator. It is designed to generate a TV signal from audio and video inputs. The MC1374’s wide dynamic range and low TV MODULATOR CIRCUIT distortion audio make it particularly well suited for applications such as video tape recorders, video disc players, TV games and subscription decoders. SEMICONDUCTOR • Single Supply, 5.0 V to 12 V TECHNICAL DATA • Channel 3 or 4 Operation • Variable Gain RF Modulator • Wide Dynamic Range • Low Intermodulation Distortion • Positive or Negative Sync 14 • Low Audio Distortion 1 • Few External Components P SUFFIX PLASTIC PACKAGE CASE 646

ORDERING INFORMATION Operating Device Temperature Range Package

MC1374P TA = 0° to +70°C Plastic DIP

Figure 1. Simplified Application V

Channel 3 4 +V = 12V 4 V + CC Pin 1 VPin 11 + S1 C8 C9 0.001 R10 0.001 R1 10k 3 470 5–25 D1 MPN3404 t C1 R3 C7 0.001 470 7 8 R7 75Ω 0.22µH 0.22µH C15 C2 L1 L3 L4 0.001 56 6 9 Output R2 C11 C12 C13 5 10 470 22 47 22 R9 4 U1 11 560 + + MC1374 D2 C14 R14 C16 1N914 R11 0.01 3 12 47 56k 220 C4 C3 + + 50 120 R4 L2 R8 C10 2 13 2.2k 10µF 6.8k R12 Video In C5 180k 0.001 1 14 + Audio In R6 R13 C6 R5 2.2k 1µF 3.3k Shaded Parts Optional 30k L1 – 4 Turns #22, 1/4″ Dia. L2 – 40 Turns, #36, 3/16″ Dia.

 Motorola, Inc. 1996 Rev 0 MOTOROLA ANALOG IC DEVICE DATA 1 MC1374

MAXIMUM RATINGS (TA = 25°C, unless otherwise noted.) Rating Value Unit Supply Voltage 14 Vdc Operating Ambient Temperature Range 0 to +70 °C Storage Temperature Range –65 to +150 °C Junction Temperature 150 °C Power Dissipation Package 1.25 W Derate above 25°C 10 mW/°C

ELECTRICAL CHARACTERISTICS (VCC = 12 Vdc, TA = 25°C, fc = 67.25 MHz, Figure 4 circuit, unless otherwise noted.) Characteristics Min Typ Max Unit AM OSCILLATOR/MODULATOR Operating Supply Voltage 5.0 12 12 V Supply Current (Figure 1) – 13 – mA Video Input Dynamic Range (Sync Amplitude) 0.25 1.0 1.0 V Pk RF Output (Pin 9, R7 = 75 Ω, No External Load) – 170 – mV pp Carrier Suppression 36 40 – dB Linearity (75% to 12.5% Carrier, 15 kHz to 3.58 MHz) – – 2.0 % Differential Gain Distortion (IRE Test Signal) 5.0 7.0 10 % Differential Phase Distortion (3.58 MHz IRE Test Signal) – 1.5 2.0 Degrees 920 kHz Beat (3.58 MHz @ 30%, 4.5 MHz @ 25%) – –57 – dB Video Bandwidth (75 Ω Input Source) 30 – – MHz Oscillator Frequency Range – 105 – MHz Internal Resistance across Tank (Pin 6 to Pin 7) – 1.8 – kΩ Internal Capacitance across Tank (Pin 6 to Pin 7) – 4.0 – pF

ELECTRICAL CHARACTERISTICS (TA = 25°C, VCC = 12 Vdc, 4.5 MHz, Test circuit of Figure 11, unless otherwise noted.) Characteristics Min Typ Max Unit FM OSCILLATOR/MODULATOR Frequency Range of Modulator 14 4.5 14 MHz Frequency Shift versus Temperature (Pin 14 open) – 0.2 0.3 kHz/°C Frequency Shift versus VCC (Pin 14 open) – – 4.0 kHz/V Output Amplitude (Pin 3 not loaded) – 900 – mVpp Output Harmonics, Unmodulated – – –40 dB Sensitivity 1.7 MHz – 0.20 – MHz/V 4.5 MHz – 0.24 – 10.7 MHz – 0.80 – Audio Distortion (±25 kHz Deviation, Optimized Bias Pin 14) – 0.6 1.0 % Audio Distortion (±25 kHz Deviation, Pin 14 self biased) – 1.4 – Incidental AM (±25 kHz FM) – 2.0 – Audio Input Resistance (Pin 14 to ground) – 6.0 – kΩ Audio Input Capacitance (Pin 14 to ground) – 5.0 – pF

Stray Tuning Capacitance (Pin 3 to ground) – 5.0 – pF Effective Oscillator Source Impedance (Pin 3 to load) – 2.0 – kΩ

2 MOTOROLA ANALOG IC DEVICE DATA MC1374

Figure 2. TV Modulator

Bias FM Oscillator/Modulator AM Modulator AM Oscillator Section Sound Carrier Sound Carrier Audio In OSC B+ Oscillator VCC RF Out RF Tank 14 4 3 2 8 9 7 6

R10 R11 R12 R16 6.0k Q7 Q21 Q22 Q1 Q2 R13 325 Q19 Q20 Q12 Q13 Q14 Q15 R17 Q25 C1 Q24 R14 Q3 Q6 Q4 Q5 Q10 Q11 R15

Q26 Q27 Q8 Q9 Q16 Q17 Q23 Q18

D1 1 1 2 R1 R2 R3 R4 R5I = 1.15 mA R6I = 1.15 mA R7 R8I = 1.15 mA R9

5 1131211 Gnd Sound Carrier Gain Video In In

GENERAL INFORMATION

The MC1374 contains an RF oscillator, RF modulator, and base station (1.76 MHz), and high enough to be used as an a phase shift type FM modulator, arranged to permit good FM IF test signal source (10.7 MHz). At 4.5 MHz, a deviation printed circuit layout of a complete TV modulation system. of ±25 kHz can be achieved with 0.6% distortion (typical). The RF oscillator is similar to the one used in MC1373, and is In the circuit above, devices Q1 through Q7 are active in coupled internally in the same way. Its frequency is controlled the oscillator function. Differential amplifier Q3, Q4, Q5, and by an external tank on Pins 6 and 7, or by a crystal circuit, and Q6 acts as a gain stage, sinking current from input section will operate to approximately 105 MHz. The video modulator Q1, Q2 and the phase shift network R17, C1. Input amplifier is a balanced type as used in the well known MC1496. Q1, Q2 can vary the amount of “in phase” Q4 current to be Modulated sound carrier and information combined with phase shifter current in load resistor R16. The can be put in separately on Pins 1 and 11 to minimize R16 voltage is applied to emitter follower Q7 which drives an unwanted crosstalk. A single resistor on Pins 12 and 13 is external L–C circuit. Feedback from the center of the L–C selected to set the modulator gain. The RF output at Pin 9 is circuit back to the base of Q6 closes the loop. As audio input a current source which drives a load connected from Pin 9 to is applied which would offset the stable oscillatory phase, the VCC. frequency changes to counteract. The input to Pin 14 can The FM system was designed specifically for the TV include a dc feedback current for AFC over a limited range. intercarrier function. For circuit economy, one phase shift The modulated FM signal from Pin 3 is coupled to Pin 1 of circuit was built into the ship. Still, it will operate from 1.4 MHz the RF modulator and is then modulated onto the AM carrier. to 14 MHz, low enough to be used in a cordless telephone

MOTOROLA ANALOG IC DEVICE DATA 3 MC1374

AM Section The AM modulator transfer function in Figure 3 shows that In , one of the most serious concerns is the the video input can be of either polarity (and can be applied at prevention of the intermodulation of color (3.58 MHz) and either input). When the voltages on Pin 1 and Pin 11 are sound (4.5 MHz) frequencies, which causes a 920 kHz signal equal, the RF output is theoretically zero. As the difference to appear in the spectrum. Very little (3rd order) nonlinearity is between VPin 11 and VPin 1 increases, the RF output needed to cause this problem. The results in Figure 6 are increases linearly until all of the current from both I1 current unsatisfactory, and demonstrate that too much of the sources (Q8 and Q9) is flowing in one side of the modulator. available dynamic range of the MC1374 has been used. This occurs when ±(VPin11 – VPin1) = I1 RG, where I1 is Figures 8 and 10 show that by either reducing standard typically 1.15 mA. The peak–to–peak RF output is the 2I1 RL. signal level, or reducing gain, acceptable results may be Usually the value of RL is chosen to be 75 Ω to ease the obtained. design of the output filter and match into TV distribution At VHF frequencies, small imbalances within the device systems. The theoretical range of input voltage and RG is introduce substantial amounts of 2nd harmonic in the RF quite wide, but noise and available sound level limit the useful output. At 67 MHz, the 2nd harmonic is only 6 to 8 dB below video (sync tip) amplitude to between 0.25 Vpk and 1.0 Vpk. the maximum fundamental. For this reason, a double pi low It is recommended that the value of RG be chosen so that pass filter is shown in the test circuit of Figure 3 and works only about half of the dynamic range will be used at sync tip well for Channel 3 and 4 lab work. For a fully commercial level. application, a vestigial sideband filter will be required. The The operating window of Figure 5 shows a cross–hatched general form and approximate values are shown in Figure 19. area where Pin 1 and Pin 11 voltages must always be in order It must be exactly aligned to the particular channel. to avoid saturation in any part of the modulator. The letter φ represents one diode drop, or about 0.75 V. The oscillator Figure 3. AM Modulator Transfer Function Pins 6 and 7 must be biased to a level of VCC – φ – 2I1 RL (or lower) and the input Pins 1 and 11 must always be at least 2φ below that. It is permissible to operate down to 1.6 V, saturating the current sources, but whenever possible, the minimum should be 3φ above ground. 2I R The oscillator will operate dependably up to about 1 L 105 MHz with a broad range of tank circuit component values. It is desirable to use a small L and a large C to minimize the dependence on IC internal capacitance. An V(p–p) operating Q between 10 and 20 is recommended. The values RF Output of R1, R2 and R3 are chosen to produce the desired Q and to set the Pin 6 and 7 dc voltage as discussed above. –I1RG 0 +I1RG Unbalanced operation, i.e., Pin 6 or 7 bypassed to ground, is Differential Input, V11–V1 (V) not recommended. Although the oscillator will still run, and the modulator will produce a useable signal, this mode causes substantial base–band video feedthrough. Bandswitching, as Figure 1 shows, can still be accomplished Figure 4. AM Test Circuit economically without using the unbalanced method. R2 The oscillator frequency with respect to temperature in the 470 test circuit shows less than ±20 kHz total shift from 0° to 50°C 0.1µH as shown in Figure 7. At higher temperatures the slope L1 ° 0.001 approaches 2.0 kHz/ C. Improvement in this region would 470 require a temperature compensating tuning capacitor of the C2 56 R3 N75 family. R1 Crystal control is feasible using the circuit shown in Figure 470 21. The crystal is a 3rd overtone series type, used in series 6 7 resonance. The L1, C2 resonance is adjusted well below the V 1 8 V crystal frequency and is sufficiently tolerant to permit fixed 1 CC values. A frequency shift versus temperature of less than 1.0 Hz/°C can be expected from this approach. The resistors RL µ 75 Ra and Rb are to suppress parasitic resonances. 10 F RF + Coupling of output RF to wiring and components on Pins 1 11 9 µ µ and 11 can cause as much as 300 kHz shift in carrier (at Video 22 H22H 67 MHz) over the video input range. A careful layout can Input 22 47 22 keep this shift below 10 kHz. Oscillator may also be 1.0k 12 13 5 inadvertently coupled to the RF output, with the undesired effect of preventing a good null when V11 = V1. Reasonable care will yield carrier rejection ratios of 36 to 40 dB below sync V11 RG tip level carrier.

4 MOTOROLA ANALOG IC DEVICE DATA MC1374

) Figure 5. The Operating Window Figure 6. 920 kHz Beat 12 0 Ω RL = 75 Initial Video = 1.0 Vdc 11 I = 1.15 mA 1 V –10 Chroma (3.58 MHz) = 300 mVpp 10 CC VCC – 2I1RL Sound (4.5 MHz) a) = 250 mVpp

9.0 [dB] –20 VCC – φ – 2I1RL b) = 500 mVpp 8.0 Gain Resistor R = 1.0 kΩ VCC – 3φ – 2I1RL –30 G 7.0 3φ 6.0 –40 Recommended b 5.0 V1 & V11 Operating Region –50 4.0 a

3.0 (fc) AMPLITUDE –60 2.0 Absolute Min = 1.6 V ± (fcAMPLITUDE 920 kHz) 1.0 (2φ + Sat) –70 0 –80 5.0 6.0 7.0 8.0 9.0 10 11 12 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 AM MODULATOR INPUT VOLTAGE PIN 1 OR PIN 11 (V PIN 1 OR 11 VOLTAGE INPUT MODULATOR AM VCC, SUPPLY VOLTAGE (Vdc) DIFFERENTIAL INPUT (V11 – V1) [Vdc)

Figure 7. RF Oscillator Frequency versus Temperature Figure 8. 920 kHz Beat 10 0 ≈ 0 fc 61.25 MHz –10 Initial Video = 0.5 Vdc VCC = 12 Vdc Chroma (3.58 MHz) = 150 mVpp

–10 [dB] –20 Sound (4.5 MHz) a) = 125 mVpp b) = 250 mVpp –20 –30 Gain Resistor RG = 1.0 kΩ –30 –40

–40 –50 b

–50 (fc) AMPLITUDE –60 FREQUENCY SHIFT (kHz) SHIFT FREQUENCY ± a

–60 (fcAMPLITUDE 920 kHz) –70

–70 –80 0 25 50 75 100 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 TA, AMBIENT TEMPERATURE (°C) DIFFERENTIAL INPUT (V11 – V1) [Vdc)

Figure 9. RF Oscillator Frequency versus Supply Voltage Figure 10. 920 kHz Beat 10 0

0 –10 Initial Video = 1.0 Vdc Chroma (3.58 MHz) = 300 mVpp

–10 [dB] –20 Sound (4.5 MHz) a) = 250 mVpp b) = 500 mVpp –20 –30 Gain Resistor (RG) = 2.2 kΩ –30 –40

–40 –50 b ° –50 TA = 25 C (fc) AMPLITUDE –60

fc = 61.25 MHz ± a NORMALIZED FREQUENCY NORMALIZED FREQUENCY (kHz) –60 (fcAMPLITUDE 920 kHz) –70

–70 –80 5.0 6.0 7.0 8.0 9.0 10 11 12 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.5 1.6 1.8 2.0 2.2 2.4 2.8 V , SUPPLY VOLTAGE (V) CC DIFFERENTIAL INPUT (V11 – V1) [Vdc)

MOTOROLA ANALOG IC DEVICE DATA 5 MC1374

FM Section The oscillator center is approximately the resonance of the The source impedance of Pin 3 is approximately 2.0 kΩ, and inductor L2 from Pin 2 to Pin 3 and the effective capacitance the open circuit amplitude is about 900 mV pp for the test C3 from Pin 3 to ground. For overall oscillator stability, it is circuit shown in Figure 11. best to keep XL in the range of 300 Ω to 1.0 kΩ. The application circuit of Figure 1 shows the The modulator transfer characteristic at 4.5 MHz is shown recommended approach to coupling the FM output from Pin 3 in Figure 15. Transfer curves at other frequencies have a very to the AM modulator input, Pin 1. The input impedance at Pin similar shape, but differ in deviation per input volt, as shown in 1 is very high, so the intercarrier level is determined by the Figures 13 and 17. source impedance of Pin 3 driving through C4 into the video Most applications will not require DC connection to the bias circuit impedance of R4 and R5, about 2.2 k. This audio input, Pin 14. However, some improvements can be provides an intercarrier level of 500 mV pp, which is correct achieved by the addition of biasing circuitry. The unaided for the 1.0 V peak video level chosen in this design. Resistor device will establish its own Pin 14 bias at 4 θ, or about 3.0 V. R6 and the input capacitance of Pin 1 provide some This bias is a little too high for optimum modulation linearity. decoupling of stray pickup of RF oscillator or AM output which Figure 14 shows better than 2 to 1 improvement in distortion may be coupled to the sound circuitry. between the unaided device and pulling Pin 14 down to 2.6 V to 2.7 V. This can be accomplished by a simple divider, if the supply voltage is relatively constant. Figure 11. FM Test Circuit The impedance of the divider has a bearing on the f C3 L2 frequency versus temperature stability of the FM system. A o (MHz) (pF) (µH) VCC divider of 180 kΩ and 30 kΩ (for VCC = 12 V) will give good temperature stabilization results. However, as Figure 18 10.7 12 10 shows, a divider is not a good method if the supply voltage 4.5 120 10 varies. The designer must make the decisions here, based 1.76 200 40 on considerations of economy, distortion and temperature 7 8 requirements and power supply capability. If the distortion C14 requirements are not stringent, then no bias components are 0.01µF 6 9 needed. If, in this case, the temperature compensation needs to be improved in the high ambient area, the tuning capacitor 5 10 from Pin 3 to ground can be selected from N75 or N150 4 11 temperature compensation types. Intercarrier L2 Sound Output 10µH Another reason for DC input to Pin 14 is the possibility of 3 12 (Use FET Probe) automatic frequency control. Where high accuracy of C5 C3 inter–carrier frequency is required, it may be desirable to feed 2 13 R12 C6 120pF back the DC output of an AFC or phase detector for nominal 0.001 + 1µF µF 1 14 carrier frequency control. Only limited control range could be Audio used without adversely affecting the distortion performance, Input R13 but very little frequency compensation will be needed. Optional Bias R One added convenience in the FM section is the separate (See Text) Pin “oscillator B+” which permits disabling of the sound system during alignment of the AM section. Usually it can be hard wired to the VCC source without decoupling. Figure 12. Modulator Sensitivity Standard practice in television is to provide pre–emphasis 2.0 of higher audio frequencies at the and a matching de–emphasis in the TV receiver audio amplifier. The purpose 1.8 of this is to counteract the fact that less energy is usually 1.6 TA = 25°C present in the higher frequencies, and also that fewer 1.4 modulation sidebands are within the deviation window. Both 1.2 factors degrade signal to noise ration. Pre–emphasis of 75 µs in 1.0 is standard practice. For cases where it has not been provided, a suitable pre–emphasis network is covered in ∆∆ 0.8 Figure 20. 0.6

It would seem natural to take the FM system output from SLOPE ( f/ V ) (MHz/V) 0.4 Pin 2, the emitter follower output, but this output is high in MAXIMUM CENTER-FREQUENCY 0.2 harmonic content. Taking the output from Pin 3 sacrifices 0 somewhat in source impedance but results in a clean output 1.4 2.0 3.04.0 5.0 6.0 7.0 8.0 9.0 10 14 fundamental, with all harmonics more than 40 dB down. This fosc, OSCILLATOR FREQUENCY [MHz] choice removes the need for additional filtering components.

6 MOTOROLA ANALOG IC DEVICE DATA MC1374

Figure 13. Modulator Transfer Function Figure 14. Distortion versus Modulation Depth 2.1 5.0 T = 25°C A VCC = 12 V 2.0 (1.76 MHz) VCC = 12 V TA = 25°C 4.0 f = 4.5 MHz 1.9 c VCC = 5.0 V, 9.0 V 1.8 3.0 Self Bias (2.9–3.0 V) 1.7

1.6 2.0

DISTORTION (%) DISTORTION Optimum Bias (2.6–2.7 V) 1.5 1.0 , OSCILLATOR FREQUENCY (MHz) FREQUENCY , OSCILLATOR 1.4 osc f 1.3 0 0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 0 255075100 DC INPUT VOLTAGE, PIN 14 (V) DEVIATION (kHz)

Figure 16. FM System Frequency Figure 15. Modulator Transfer Function versus Temperature

4.9 4.55 TA = 25°C V = 12 V 4.8 (4.5 MHz) CC 4.54 VCC = 12 V 4.7 4.53 VCC = 5.0 V, 9.0 V Pin 14 V to 2.6 V 4.6 4.52

4.5 4.51 180 k/30 k Divider 4.4 4.50

4.3 (MHz) f, FREQUENCY 4.49 Pin 14 Open , OSCILLATOR FREQUENCY (MHz) FREQUENCY , OSCILLATOR 4.2 4.48 osc f 4.1 4.47 0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 0 255075100 DC INPUT VOLTAGE, PIN 14 (V) TA, AMBIENT TEMPERATURE (°C)

Figure 17. Modulator Transfer Function Figure 18. FM System Frequency versus VCC 11.6 4.50 T = 25°C 12 V Pin 14 to 2.6 V Source A 9.0 V VCC 11.4 (10.7 MHz) 5.0 V 4.49 11.2 4.48 11.0 Pin 14 Open 4.47 10.8 10.6 4.46 Pin14 – 180 k/ 30 k Divider 10.4 4.45 10.2

f, FREQUENCY (MHz) f, FREQUENCY 4.44 10.0 ° , OSCILLATOR FREQUENCY (MHz) FREQUENCY , OSCILLATOR TA = 25 C 4.43

osc 9.8 f 9.6 4.42 0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 4.0 5.0 6.0 7.0 8.0 9.0 10 11 12 DC INPUT VOLTAGE, PIN 14 (V) VCC, SUPPLY VOLTAGE (Vdc)

MOTOROLA ANALOG IC DEVICE DATA 7 MC1374

Figure 19. A Channel 4 Vestigial Sideband Filter VCC

8 Both transformer windings 0 Ω 4T #23 AWG –10 9 RL = 75 8.2pF close wound on 1/4″ ID –20 Ω 39 on common axis, 3/8″ spacing. 24 2.7k –30 pF –40 33pF Ch. 4 Ch. 4 8.2pF Ω Ω –50 Pix S 24 24 Output –60 Ω (dB) ATTENUATION 75 –70 33pF 33pF 100Ω 61 65 69 73 f, FREQUENCY (MHz) 8T #23 AWG close wound on 1/8″ ID, knife tuned to trap Channel 3 61.25 MHz.

Figure 20. Audio Pre–Emphasis Circuit 1 25 2 π RC 20 C = 0.0012µF 15 C = 0.1µF C 1 –+ 14 10 1 2 π rC “Flat” Audio R 5 2 π (r + R)CC Input 6.0kΩ Audio r = 56kΩ Input 0 5 Gnd RELATIVE OUTPUT/INPUT (dB) OUTPUT/INPUT RELATIVE –5 21 210 2100 21k f, FREQUENCY (MHz) 1 Pre–emphasis = 75 µs = rC = 2 π (2100 Hz)

Figure 21. Crystal Controlled RF Oscillator for Channel 3, 61.25 MHz

VCC

R1 470

C1 R2 470 0.001 R3 470 61.252 MHz C2

56pF Ra 180 L1

0.15µH Rb 18 6 7

MC1374

NOTE: See Application Note AN829 for further information.

8 MOTOROLA ANALOG IC DEVICE DATA MC1374

OUTLINE DIMENSIONS

P SUFFIX PLASTIC PACKAGE CASE 646–06 NOTES: ISSUE L 1. LEADS WITHIN 0.13 (0.005) RADIUS OF TRUE 14 8 POSITION AT SEATING PLANE AT MAXIMUM MATERIAL CONDITION. B 2. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 17 3. DIMENSION B DOES NOT INCLUDE MOLD FLASH. 4. ROUNDED CORNERS OPTIONAL. A INCHES MILLIMETERS DIM MIN MAX MIN MAX F L A 0.715 0.770 18.16 19.56 B 0.240 0.260 6.10 6.60 C 0.145 0.185 3.69 4.69 D 0.015 0.021 0.38 0.53 C F 0.040 0.070 1.02 1.78 G 0.100 BSC 2.54 BSC J H 0.052 0.095 1.32 2.41 N J 0.008 0.015 0.20 0.38 K 0.115 0.135 2.92 3.43 SEATING PLANE K L 0.300 BSC 7.62 BSC HG D M M 0 ____ 10 0 10 N 0.015 0.039 0.39 1.01

MOTOROLA ANALOG IC DEVICE DATA 9 MC1374

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